The TELEFUNKEN CHASSIS 712A was introducing first time a SMPS POWER SUPPLY and chroma combined 3 chips design in video sections and further using the 20AX SYSTEM CRT TUBE BUT HERE MADE BY TELEFUNKEN FACTORY.
It's mainly a modular chassis and highly sophisticated and complex.
This chassis THE TELEFUNKEN CHASSIS 712A was even featuring a DYNAMIC FOCUS in the Line deflection EHT circuitry.
Dynamic focus voltages for a CRT are obtained by utilizing the combined parabolic conversion wave shapes for control of the focusing electrode to provide sharp focus at all points in the raster. A current source is coupled to the focus divider chain and the conversion wave shape controls the current in the divider chain by controlling the resistance in a transistor. No high voltage capacitors are required since the dynamic voltages are coupled into the chain near the low voltage end. 1. In a cathode ray tube device for displaying information by means of a raster:
a cathode ray tube having an anode and a focus electrode;
an input source of AC voltage having variations of substantially parabolic waveform at both horizontal and vertical rates;
a source of high voltage DC coupled to the anode;
transistor means for amplifying said input AC voltage and coupled to ground and to the ac input source; and
resistive means including first and second elements, the first element coupled between the source of high voltage and the focus electrode, the second element coupled between the focus electrode and the transistor means, the first element having a resistance substantially greater than that of the second element.
2. A cathode ray tube device for displaying information on a raster in accordance with claim 1 and wherein the resistive means also includes a manually variable resistive means. 3. A cathode ray tube device for displaying information on a raster in accordance with claim 2 wherein the manually controllable resistive means is a focus control. 4. A cathode ray tube device for displaying information on a raster in accordance with claim 1 and further including an amplifier stage coupled between the source of AC voltage and the transistor means. 5. A cathode ray tube device for displaying information on a raster in accordance with claim 1 and wherein said lower DC voltage is manually variable. 6. A cathode ray tube device for displaying information on a raster in accordance with claim 1 and further including a source of relatively low voltage DC coupled to the junction of the second resistive means element and the transistor means. 7. A cathode ray tube device for displaying information on a raster in accordance with claim 6 wherein the source of relatively low voltage DC is coupled to the junction through a clamping diode means and a biasing resistive means.
Description:
BACKGROUND OF THE INVENTION This invention relates to the field of cathode ray tubes and, more particularly, to the provision for dynamic focusing voltages for use in such tubes. In CRT devices, the major factor effecting spot focus is the variation in the distance from the electron gun to the fluorescent screen as the electron beam is swept from the center of the screen to the outer areas. For accurate focusing of the beam at all parts of the screen, the voltage applied to the focus electrode must be varied as a function of the distance from the spot to the Z axis of the CRT device, or, in other words, a function of the angle of deflection. This requires a voltage which varies as the beam moves horizontally and also as it moves vertically. As a reasonable approximation, this requires a horizontal voltage variation at line rate which is of essentially parabolic shape, and which is superimposed on a similar function at the vertical frame rate. Earlier CRT designs provided minimum spot de-focusing by optimizing focus at some point intermediate the center of the CRT screen and the edges of the raster; e.g., 30° from the Z axis was typical. Later it was recognized that a better solution would be to add to the static focusing voltage a voltage varying with the angle of deflection. All known circuits for accomplishing dynamic focusing in this way have required high voltage coupling capacitors and thus were expensive and not adaptable to solid state implementation.
SUMMARY OF THE INVENTION
It is therefore an object of the present invention to provide dynamic focusing for a CRT utilizing waveforms which are already present in the CRT device.
These objects and others are provided by circuitry constructed in accordance with the invention in which the effective resistance of a transistor circuit is varied as a function of the convergence waveform. The transistor circuit is coupled in series with the focus divider chain, thus the current in the chain is varied accordingly. No high voltage capacitors are required for coupling the dynamic focus voltage to the CRT device since the transistor is near the low voltage end of the divider chain. The convergence waveform is a combination of two waveforms, one at line rate and one at frame rate, each essentially of parabolic form.
BRIEF DESCRIPTION OF THE DRAWING
FIG. 1a is a diagram of a CRT device showing the dimensional basis for the problem which is solved by the invention.
FIG. 1b is a diagram of a dot pattern of a CRT device lacking the circuit of the invention.
FIGS. 2a-2c are illustrations of the voltage waveforms required for the invention.
FIG. 3 is a block diagram of a device utilizing a CRT and including the invention.
FIG. 4 is an embodiment of the circuitry of the invention.
DETAILED DESCRIPTION OF THE PREFERRED EMBODIMENT
The diagram of FIG. 1a is intended
to make clear the problem to be solved by the circuit of the invention. A 3-gun cathode ray tube (CRT) 10 of the type used in color television is shown in outline form. Such tubes typically have a rounded face plate or screen 11 (bearing the phosphors) with a radius of curvature R' longer than the entire tube length, however, the invention is applicable even to flat face plate tubes. The electron beam thus travels a path R2 from the point of deflection B to the edges of the screen 11 which is longer than the path R1 to the central portion, ΔR being the instantaneous difference. It will be seen then that the focusing voltage must be adjusted to compensate for this difference as the electron beam is swept from side to side and top to bottom of a raster. FIG. 1b is a graphical representation of the spot defocusing which occurs at the outer portions of a CRT screen if dynamic focusing is not used. Instead of providing a sharp focus spot, as at the center of the screen, a small circle is produced which reduces the definition of the displayed information.
FIG. 2 shows the types of waveforms needed to provided dynamic focusing and eliminate the de-focusing effect of FIG. 1b. As may be seen in FIG. 2a, a roughly parabolic waveform repeating at frame rate, is needed for the vertical dimension. A similar waveform, FIG. 2b, but repeating at line rate, is needed for the horizontal dimension. FIG. 2c illustrates the combined waveform with the horizontal rate greatly reduced for clarity. As may be seen, no dynamic focusing voltage is applied as the electron beam sweeps the central portion of the screen. FIG. 3 is a block diagram of a typical video receiver utilizing a raster to display information and is given here only for a better understanding of the invention as the invention could, for example, be utilized in a monitor which lacks much of this circuitry. The RF amplifier 12, local oscillator 13, mixer 14, IF amplifier 15, detector 16, sound portion 17, video amplifier 18 and color demodulator 19 all function as is well known in the art. The detector 16 output is also coupled to sync circuits 20, which provide synchronization for vertical and horizontal sweep circuits 21 and 22 respectively. The sync signals are coupled to the CRT 10 for providing a raster on the screen 11 of the tube. The sweep circuits 21 and 22 are also coupled to a convergence circuit 24 which is coupled to the CRT 10.
The vertical and horizontal sweep circuits 21 and 22 are coupled to the convergence circuit 24 which is connected to the convergence coil of the CRT 10. In this embodiment of the invention the convergence circuit 24 is also coupled through a dynamic focus circuit 26 to the focus circuit 27 which is coupled to the CRT 10.
FIG. 4 is a schematic diagram of one embodiment of the dynamic focus circuit of the invention. The terminal 30 is coupled to an amplifier including a transistor Q1. The terminal 30 could be coupled through the
convergence circuit 24 as shown in FIG. 3 or from the pin cushion circuitry (not shown) which also has the vertical rate parabolic waveform. A terminal 31 may couple an input signal, as from the convergence circuit, which has the desired parabolic waveform at the horizontal or line rate. A terminal 33 is coupled to a high voltage source; i.e., the CRT anode voltage supply. Forming a voltage divider across the high voltage is a tapped resistor R1, a potentiometer or variable resistor R2 (the "focus" control) and a transistor Q2. The tap on resistor R1 is coupled to the focus electrode of the CRT by way of a terminal 34. It will be seen that the voltage on the terminal 34 can be varied or modulated by varying the effective resistance of the transistor Q2. A low voltage is coupled from a terminal 36 to the collector of the transistor Q2 by way of a biasing transistor R3 and a clamping diode D1. The voltage on terminal 36 is preferably a variable voltage to provide for the slight variations which occur from one CRT to another. A resistor R4 provides a feedback path, and a resistor R5 and a capacitor C1 provide the necessary time constant. Once the focus control R2 is set to provide minimum beam spot size at the center of the screen, the added voltage, having parabolic waveforms at both horizontal and vertical rate, will optimize the focusing at the edges of the raster. Thus, there has been shown and described a means of providing dynamic focusing for a CRT by using a voltage such as the pin cushion correction voltage or the dynamic convergence voltage to control the effective resistance of a solid state circuit which in turn controls the current in the focus circuit of a CRT.
It will be apparent that there are a number of variations and modifications of the above-described embodiment and it is intended to include all such as fall within the spirit and scope of the appended claims.
TELEFUNKEN PALCOLOR 8812 SUPERCONTROL 26 CHASSIS 712A POWER SUPPLY UTILIZING A DIODE AND CAPACITOR VOLTAGE MULTIPLIER FOR TRACKING FOCUSING AND ULTOR VOLTAGES
A television receiver high voltage power supply includes an ultor voltage output and an output voltage at some potential lower than the ultor voltage. The supply is responsive to kinescope beam current to vary the proportionate magnitudes of the high and lower voltages at some predetermined ratio.
1. In a television receiver electron beam deflection system, a power supply comprising: 2. A circuit as defined in claim 1 wherein said voltage multiplying means comprise at least: 3. A circuit as defined in claim 1 wherein: 4. A circuit as defined in claim 3 wherein said lower voltage output means further comprises: 5. A circuit as defined in claim 1 wherein said lower output voltage means comprises a focus voltage supply in a television receiver. 6. In a television receiver electron beam deflection circuit, a power supply comprising: 7. A circuit as defined in claim 6 and further comprising: 8. A circuit as defined in claim 6 wherein said lower output voltage means comprises a focus voltage in a television receiver.
Description:
POWER SUPPLY
This invention relates to high direct voltage power supplies and more particularly to television receiver high voltage and focus voltage supplies employing voltage multiplier arrangements.
In a television receiver, electron beam focusing in the kinescope is commonly achieved by utilizing an electr
ostatic focusing lens. For optimum focusing, it is necessary to vary the strength of the focusing lens with varying beam current and electron velocity (i.e., electron beam accelerating voltage). The focusing lens may comprise, for example, a pair of cylindrically shaped members mounted along the kinescope gun axis and having a separating space between them. Focusing is accomplished by the electric field produced by the geometry of the focusing members and the potential difference between them --that is, by the shape and magnitude of the focusing field. In order to maintain a beam or beams of electrons in optimum focus under varying beam current conditions and differing electron beam velocities, it is necessary to vary the focusing field. Since the geometry of the focusing members is fixed, it is necessary to adjust the voltage difference between these members to effect proper focusing.
As beam current increases, if the high voltage (the accelerating potential of the electron beam) remains substantially constant, as is the case with a regulated high voltage supply, a stronger focusing lens is needed to maintain focusing of the electron beam. The strength of the focusing lens can be increased, where, as in a color television receiver, the focusing members are coupled to a focus voltage supply and the high beam-accelerating voltage supply, respectively, by decreasing the output of the focus voltage supply to increase the potential gradient across the focusing lens. Thus, if the high voltage is constant and the beam current increases, the focus voltage as a percentage of the high voltage should be decreased to maintain focus at high beam current levels. Further, if the high voltage (electron-accelerating potential) is not maintained constant but decreases somewhat, and therefore the electron velocity decreases as beam current increases, the strength of the focusing lens should be increased which again requires a reduction in focus voltage. The percentage reduction in focus voltage customarily is equal to or greater than the corresponding percentage reduction in high voltage. This effect is commonly referred to as "focus tracking."
In television receivers, it is common to develop the high voltage from a secondary winding on the horizontal deflection output transformer. The flyback pulses developed during horizontal retrace are stepped up by the flyback transformer and rectified to produce the necessary high voltage. Further, it is common to provide separate rectifying means coupled to a lower voltage tap on the flyback transformer, to develop a focus voltage in a color television receiver.
U.S. Pat. No. 2,879,447 (issued to J. O. Preisig) assigned to the present assignee discloses such an arrangement including means for obtaining the necessary "focus tracking" described above.
The present invention obviates the need for separate transformer windings for the high voltage and focus voltage supplies but provides the desired focus tracking while deriving both high voltage (beam-accelerating voltage) and focus voltage from a common point on the horizontal output transformer by means of a voltage multiplier arrangement.
Circuits embodying the present invention include a horizontal output transformer having a high voltage winding, voltage-multiplying means coupled to the high voltage winding for producing the ultor voltage for a television receiver, and lower voltage output means associated with the voltage multiplying means and responsive to beam current for producing a voltage which tracks with the ultor voltage.
A better understanding of the present invention and its features and advantages can be obtained by reference to the single FIGURE and the description below.
In the drawing, a voltage supply constructed in accordance with the present invention is illustrated partially in block and partially in schematic form.
Referring to the FIGURE, horizontal deflection circuits 10 include a horizontal output stage (not shown) which produces a generally sawtooth current waveform characterized by a relatively slow rise time during a trace portion of each deflection cycle and a relatively rapid fall time during a retrace portion of each deflection cycle. For clarity, the deflection windings and associated horizontal output circuitry are not shown. Such a circuit is shown in detail in RCA Television Service Data 1968 No. 20, published by RCA Sales Corporation, Indianapolis, Indiana. It is sufficient for the purposes of the present invention to note that during the retrace portion of each deflection cycle, energy in the form of a voltage pulse commonly referred to as a flyback pulse is coupled by means of a primary winding 11 of a horizontal output transformer 12 to a secondary winding 13 thereof. The turns ratio of transformer 12 is selected to step up the voltage of this flyback pulse appearing at a high voltage terminal 14 on secondary winding 13. The voltage magnitude of this flyback pulse is partially dependent upon the turns ratio of transformer 12 and in the circuit illustrated is of the order of 6.25 kilovolts. This will produce an ultor voltage (V 1 ) of approximately 25 kilovolts at ultor output terminal 40 when applied to the voltage quadrupler described below.
The voltage multiplier may be designed to multiply by any number n by adding or subtracting successive stages of multiplication. Thus, the necessary stepped up flyback voltage magnitude will be approximately V 1 /n where V 1 is the desired ultor voltage at terminal 40 and n is the num
ber of stages of multiplication.
When the system is initially put into operation, positive flyback pulses will cause a first undirectional conductive device such as a diode 18 to be forward biased and conduct to charge a focus output charge storage device such as a capacitor 21 in the polarity shown and at a potential nearly equal to the peak flyback voltage appearing at high voltage terminal 14. As the flyback pulse decreases from its peak value, a second unidirectional conductive device 20 will then be forward biased, since its anode connected to terminal 50 will be more positive than its cathode, the latter being at the same voltage as terminal 14 at this time. When device 20 conducts, at least a portion of the charge on the output or focus charge storage device 21 is transferred to a first charge storage device 15 in the polarity shown. The transfer of charge continues during successive deflection cycles by the conduction of a third unidirectional conductive device 22 to charge a second charge storage device 23, the conduction of a fourth unidirectional conductive device 24 to charge a third charge storage device 17, the conduction of a fifth unidirectional conductive device 26 to charge a fourth charge storage device 25, the conduction of a sixth unidirectional conductive device 28 to charge a fifth charge storage device 19, and the conduction of a seventh unidirectional conductive device 30 to charge a final charge storage device 27. Assuming there are no losses within the system and no current is being drawn from the system as successive flyback pulses occur, the charge storage de
vices mentioned, with the exception of devices 15 and 21 as will be explained below, will each become charged to approximately the peak to peak value of the transformed flyback pulse waveform illustrated on the drawing. The charge storage device 21 charges only during the positive flyback pulse portion of the waveform and, as a consequence of a resistor 16 coupled in series with conductive device 18, charges to a voltage less than the peak amplitude of the flyback pulse. Therefore, when conductive device 20 conducts, storage device 15 charges to a voltage equal to the voltage across storage device 21 plus the negative voltage at terminal 14 occurring between flyback pulses (i.e., less than the peak-to-peak value of the waveform at terminal 14 by, for example, 200 volts). Adding the series voltages across charge storage devices 21, 23, 25 and 27, the output voltage at terminal 40 will be approximately three times the peak to peak flyback voltage plus the voltage across storage device 21 or almost four times the peak-to-peak flyback voltage. Kinescope charge storage device 29, illustrated in dotted lines, is the capacitance of the aquadag coating on the associated kinescope to ground. A resistance 31 is serially coupled from the final charge storage device 27 to an output terminal 40 and serves as a current-limiting resistance to protect the horizontal output circuit in the event of kinescope arcing.
As current is drawn from the system due to a flow of beam current within the kinescope, charge storage devices 21, 23, 25, 27 and 29 begin to discharge to supply the output current. As this occurs, the voltage across these devices will decrease. The unidirectional conductive devices 22, 26 and 30 conduct to equalize the voltage across storage devices in the upper series connection (in the drawing) with those across devices in the lower series connection. The flyback pulse will be coupled via charge storage devices 15, 17 and 19 and unidirectional conductive devices 18, 20, 26 and 30 will conduct when forward biased to restore the charge on the charge storage devices. Unidirectional devices 20, 24 and 28 then conduct to again equalize voltages. A mean direct current will flow through the charge transfer unidirectional conductive devices and resistance 16 serially coupled to the first unidirectional conductive device 18. As beam current increases, this mean current increases, thus developing a larger voltage drop across resistance 16. Since the voltage at terminal 50 is approximately one-quarter that of the ultor voltage V 1 at terminal 40, and since resistance 16 is relatively large as compared with the forward resistance of the unidirectional conductive devices, the percentage decrease of the voltage V 2 present at terminal 50 will be greater than the percentage decrease of the ultor voltage present at terminal 40 for high beam current. The utilization of resistance 16 in series relation to unidirectional conductive device 18 provides the proper relationship between the focus voltage and ultor voltage. It is noted that although resistance 16 is illustrated as a separate element, it may be incorporated within a unidirectional conductive device as for example, one having a higher forward resistance than the remaining devices 20, 22, 24, 26, 28 and 30.
A voltage dividing network comprising resistors 32, 34 and 36 serially coupled from terminal 50 to ground provide a network from which an adjustable voltage V 3 can be extracted by means of a variable resistor 34.
Although the present invention is particularly suitable for focus tracking applications, it may be useful wherever a voltage which is responsive to beam current is desired.
The parameters listed below have been utilized in the preferred embodiment.
Capacitors 15, 17, 19 21, 23, 25, 27 2,000 picofarads Capacitor 29 2,500 picofarads Resistors 16 22 kiloohms 31 10 kiloohms Resistors 32 5 megohms 34 15 megohms 36 30 megohms Diodes 18, 20, 22 9 kilovolt peak inverse voltage,5 milliamp 24,26,28,30 5 ampere surge.
Arentsen et al, Electronic Applications, vol. 34, No. 2, Philips Semiconductor Application Lab., pp. 52-60.
Loewe Opta, Circuit Schematic, Aug. 1st, 1980.
Thomson-Brandt, Circuit Schematic, Apr. 15th, 1981.
Blaupunkt, Circuit Schematic, (undated).
Grundig, Circuit Schematic, (undated).
ITT, Circuit Schematic, (undated).
Telefunken, Circuit Schematic, (undated).
Schneider, Circuit Schematic, (undated).
This invention relates to high direct voltage power supplies and more particularly to television receiver high voltage and focus voltage supplies employing voltage multiplier arrangements.
In a television receiver, electron beam focusing in the kinescope is commonly achieved by utilizing an electr
ostatic focusing lens. For optimum focusing, it is necessary to vary the strength of the focusing lens with varying beam current and electron velocity (i.e., electron beam accelerating voltage). The focusing lens may comprise, for example, a pair of cylindrically shaped members mounted along the kinescope gun axis and having a separating space between them. Focusing is accomplished by the electric field produced by the geometry of the focusing members and the potential difference between them --that is, by the shape and magnitude of the focusing field. In order to maintain a beam or beams of electrons in optimum focus under varying beam current conditions and differing electron beam velocities, it is necessary to vary the focusing field. Since the geometry of the focusing members is fixed, it is necessary to adjust the voltage difference between these members to effect proper focusing.As beam current increases, if the high voltage (the accelerating potential of the electron beam) remains substantially constant, as is the case with a regulated high voltage supply, a stronger focusing lens is needed to maintain focusing of the electron beam. The strength of the focusing lens can be increased, where, as in a color television receiver, the focusing members are coupled to a focus voltage supply and the high beam-accelerating voltage supply, respectively, by decreasing the output of the focus voltage supply to increase the potential gradient across the focusing lens. Thus, if the high voltage is constant and the beam current increases, the focus voltage as a percentage of the high voltage should be decreased to maintain focus at high beam current levels. Further, if the high voltage (electron-accelerating potential) is not maintained constant but decreases somewhat, and therefore the electron velocity decreases as beam current increases, the strength of the focusing lens should be increased which again requires a reduction in focus voltage. The percentage reduction in focus voltage customarily is equal to or greater than the corresponding percentage reduction in high voltage. This effect is commonly referred to as "focus tracking."
U.S. Pat. No. 2,879,447 (issued to J. O. Preisig) assigned to the present assignee discloses such an arrangement including means for obtaining the necessary "focus tracking" described above.
The present invention obviates the need for separate transformer windings for the high voltage and focus voltage supplies but provides the desired focus tracking while deriving both high voltage (beam-accelerating voltage) and focus voltage from a common point on the horizontal output transformer by means of a voltage multiplier arrangement.
Circuits embodying the present invention include a horizontal output transformer having a high voltage winding, voltage-multiplying means coupled to the high voltage winding for producing the ultor voltage for a television receiver, and lower voltage output means associated with the voltage multiplying means and responsive to beam current for producing a voltage which tracks with the ultor voltage.
A better understanding of the present invention and its features and advantages can be obtained by reference to the single FIGURE and the description below.
In the drawing, a voltage supply constructed in accordance with the present invention is illustrated partially in block and partially in schematic form.
Referr
ing to the FIGURE, horizontal deflection circuits 10 include a horizontal output stage (not shown) which produces a generally sawtooth current waveform characterized by a relatively slow rise time during a trace portion of each deflection cycle and a relatively rapid fall time during a retrace portion of each deflection cycle. For clarity, the deflection windings and associated horizontal output circuitry are not shown. Such a circuit is shown in detail in RCA Television Service Data 1968 No. 20, published by RCA Sales Corporation, Indianapolis, Indiana. It is sufficient for the purposes of the present invention to note that during the retrace portion of each deflection cycle, energy in the form of a voltage pulse commonly referred to as a flyback pulse is coupled by means of a primary winding 11 of a horizontal output transformer 12 to a secondary winding 13 thereof. The turns ratio of transformer 12 is selected to step up the voltage of this flyback pulse appearing at a high voltage terminal 14 on secondary winding 13. The voltage magnitude of this flyback pulse is partially dependent upon the turns ratio of transformer 12 and in the circuit illustrated is of the order of 6.25 kilovolts. This will produce an ultor voltage (V 1 ) of approximately 25 kilovolts at ultor output terminal 40 when applied to the voltage quadrupler described below.The voltage multiplier may be designed to multiply by any number n by adding or subtracting successive stages of multiplication. Thus, the necessary stepped up flyback voltage magnitude will be approximately V 1 /n where V 1 is the desired ultor voltage at terminal 40 and n is the num
ber of stages of multiplication.When the system is initially put into operation, positive flyback pulses will cause a first undirectional conductive device such as a diode 18 to be forward biased and conduct to charge a focus output charge storage device such as a capacitor 21 in the polarity shown and at a potential nearly equal to the peak flyback voltage appearing at high voltage terminal 14. As the flyback pulse decreases from its peak value, a second unidirectional conductive device 20 will then be forward biased, since its anode connected to terminal 50 will be more positive than its cathode, the latter being at the same voltage as terminal 14 at this time. When device 20 conducts, at least a portion of the charge on the output or focus charge storage device 21 is transferred to a first charge storage device 15 in the polarity shown. The transfer of charge continues during successive deflection cycles by the conduction of a third unidirectional conductive device 22 to charge a second charge storage device 23, the conduction of a fourth unidirectional conductive device 24 to charge a third charge storage device 17, the conduction of a fifth unidirectional conductive device 26 to charge a fourth charge storage device 25, the conduction of a sixth unidirectional conductive device 28 to charge a fifth charge storage device 19, and the conduction of a seventh unidirectional conductive device 30 to charge a final charge storage device 27. Assuming there are no losses within the system and no current is being drawn from the system as successive flyback pulses occur, the charge storage de
vices mentioned, with the exception of devices 15 and 21 as will be explained below, will each become charged to approximately the peak to peak value of the transformed flyback pulse waveform illustrated on the drawing. The charge storage device 21 charges only during the positive flyback pulse portion of the waveform and, as a consequence of a resistor 16 coupled in series with conductive device 18, charges to a voltage less than the peak amplitude of the flyback pulse. Therefore, when conductive device 20 conducts, storage device 15 charges to a voltage equal to the voltage across storage device 21 plus the negative voltage at terminal 14 occurring between flyback pulses (i.e., less than the peak-to-peak value of the waveform at terminal 14 by, for example, 200 volts). Adding the series voltages across charge storage devices 21, 23, 25 and 27, the output voltage at terminal 40 will be approximately three times the peak to peak flyback voltage plus the voltage across storage device 21 or almost four times the peak-to-peak flyback voltage. Kinescope charge storage device 29, illustrated in dotted lines, is the capacitance of the aquadag coating on the associated kinescope to ground. A resistance 31 is serially coupled from the final charge storage device 27 to an output terminal 40 and serves as a current-limiting resistance to protect the horizontal output circuit in the event of kinescope arcing.A voltage dividing network comprising resistors 32, 34 and 36 serially coupled from terminal 50 to ground provide a network from which an adjustable voltage V 3 can be extracted by means of a variable resistor 34.
Although the present invention is particularly suitable for focus tracking applications, it may be useful wherever a voltage which is responsive to beam current is desired.
The parameters listed below have been utilized in the preferred embodiment.
Capacitors 15, 17, 19 21, 23, 25, 27 2,000 picofarads Capacitor 29 2,500 picofarads Resistors 16 22 kiloohms 31 10 kiloohms Resistors 32 5 megohms 34 15 megohms 36 30 megohms Diodes 18, 20, 22 9 kilovolt peak inverse voltage,5 milliamp 24,26,28,30 5 ampere surge.
Other References:
IBM Technical Disclosure Bulletin, vol. 17, No. 4, Sep. 1974, K. H. Knickmeyer, pp. 1091-1092. Arentsen et al, Electronic Applications, vol. 34, No. 2, Philips Semiconductor Application Lab., pp. 52-60.
Loewe Opta, Circuit Schematic, Aug. 1st, 1980.
Thomson-Brandt, Circuit Schematic, Apr. 15th, 1981.
Blaupunkt, Circuit Schematic, (undated).
Grundig, Circuit Schematic, (undated).
ITT, Circuit Schematic, (undated).
Telefunken, Circuit Schematic, (undated).
Schneider, Circuit Schematic, (undated).
A power supply voltage stabiliz
er comprising a transformer, of which the primary winding is connected to a switching means for controlling power supply to the primary winding. An oscillator circuit is associated with the switching means in order to control on/off operation of the switching means. An abnormal overvoltage and/or overcurrent detection circuit is provided for terminating the oscillation operation of the oscillator circuit when impending overvoltage and/or overcurrent is detected. 1. A power supply voltage stabilizer comprising:
a transformer including a primary winding connected to a power source and a secondary winding for output purposes;
switching means connected to said primary winding for controlling power supply to said primary winding;
an oscillator circuit for controlling on/off operation of said switching means; and
abnormal condition detection means for developing a control signal for terminating oscillation operation of said oscillator circuit when an abnormal condition is detected;
said oscillator circuit including an astable multivibrator, and variable impedance means for varying an oscillation frequency of said astable multivibrator.
2. A power supply voltage stabilizer comprising: a transformer including a primary winding connected to a power source and a secondary winding for output purposes;
switching means connected to said primary winding for controlling power supply to said primary winding;
an oscillator circuit for controlling on/off operation of said switching means; and
abnormal condition detection means for developing a control signal for terminating oscillation operation of said oscillator circuit when an abnormal condition is detected;
said transformer further including an auxiliary winding for developing a voltage proportional to that developed through said secondary winding, said voltage developed through said auxiliary winding being applied to said oscillator circuit for driving said oscillator circuit;
said abnormal condition detection means including an overvoltage detection circuit connected to said auxiliary winding for developing said control signal when an overvoltage is developed through said auxilliary winding;
said oscillator circuit comprising an astable multivibrator, and variable impedance means for varying an oscillation frequency of said astable multivibrator.
3. A power supply voltage stabilizer comprising:
a transformer including a primary winding connected to a power source and a secondary winding for output purposes;
switchi
ng means connected to said primary winding for controlling power supply to said primary winding; an oscillator circuit for controlling on/off operation of said switching means; and
abnormal condition detection means for developing a control signal for terminating oscillation operation of said oscillator circuit when an abnormal condition is detected;
said transformer further including an auxiliary winding for developing a voltage proportional to that developed through said secondary winding, said voltage developed through said auxiliary winding being applied to said oscillator circuit for driving said oscillator circuit;
said abnormal condition detec
tion means including an overvoltage detection circuit connected to said auxiliary winding for developing said control signal when an overvoltage is developed through said auxiliary winding; said overvoltage detection circuit including a latching means for continuously developing said control signal.
4. A power supply voltage stabilizer comprising:
a transformer including a primary winding connected to a power source and a secondary winding for output purposes;
switching means connected to said primary winding for controlling power supply to said primary winding;
an oscillator circuit for controlling on/off operation of said switching means;
abnormal condition detection means for developing a control signal for terminating oscillation operation of said oscillator circuit when an abnormal condition is detected;
said transformer further including an auxiliary winding for developing a voltage proportional to that developed through said secondary winding, said voltage developed through said auxiliary winding being applied to said oscillator circuit for driving said oscillator circuit;
said abnormal condition detection means including an overvoltage detection circuit connected to said auxiliary winding for developing said control signal when an overvoltage is developed through said auxiliary winding;
said overvoltage detection circui
t further includes, a reference voltage generation means for developing a reference voltage proportional to a voltage applied from said power source; and
comparing means for comparing said voltage developed through said auxiliary winding with said reference voltage in order to develop said control signal when said voltage developed through said auxiliary winding exceeds said reference voltage.
5. A power supply voltage stabilizer comprising:
a transformer including a primary winding connected to a power source and a secondary winding for output purposes;
switching means connected to said primary winding for controlling power supply to said primary winding;
an oscillator circuit for controlling on/off operation of said switching means; and
abnormal condition detection means for developing a control signal for terminating oscillation operation of said oscillator circuit when an abnormal condition is detected;
said abnormal condition detection means including an overcurrent detection circuit connected to said primary winding for developing said control signal when an overcurrent flows through said primary winding;
wherein said oscillator circuit includes an astable multivibrator, and variable impedance means for varying an oscillation frequency of said astable multivibrator.
6. A power supply voltage stabilizer comprising:
a transformer including a primary winding connected to a power source and a secondary winding for output purposes;
switching means connected to said primary winding for controlling power supply to said primary winding;
an oscillator circuit for controlling on/off operation of said switching means; and
abnormal condition detection means for developing a control signal for terminating oscillation operation of said oscillator circuit when an abnormal condition is detected;
said abnormal condition detection means including an overcurrent detection circuit connected to said primary winding for developing said control signal when an overcurrent flows through said primary winding;
said overcurrent detection circuit including a latching means for continuously developing said control signal;
said oscillator circuit including an astable multivibrator, and variable impedance means for varying an oscillation frequency of said astable multivibrator.
7. The power supply voltage stabilizer of claim 1, 2, 5, or 6, wherein said variable impedance means comprise a photo transistor, and wherein a light emitting diode is connected to said secondary wind
ing for emitting a light of which amount is proportional to a voltage developed through said secondary winding, said light emitted from said light emitting diode being applied to said photo transistor. 8. The power supply voltage stabilizer of claim 7, wherein said light emitting diode and said photo transistor are incorporated in a single photo coupler. 9. A power supply voltage stabilizer comprising: a transformer including a primary winding connected to a power source and a secondary winding for output purposes;
switching means connected to said primary winding for controlling power supply to said primary winding;
an oscillator circuit for controlling on/off operation of said switching means; and
abnormal condition detection means for developing a control signal for terminating oscillation operation of said oscillator circuit when an abnormal condition is detected;
said transformer further including an auxiliary winding for developing a voltage proportional to that developed through said secondary winding, said voltage developed through said auxiliary winding being applied to said oscillator circuit for driving said oscillator circuit;
said abnormal condition detection means including an overvoltage detection circuit connected to said auxiliary winding for developing said control signal when an overvoltage is developed through said auxilliary winding;
said overvoltage detection circuit including a latching means for continuously developing said control signal;
said oscillator circuit including an astable multivibrator, and variable impedance means for varying an oscillation frequency of said astable multivibrator.
10. A power supply voltage stabilizer comprising:
a transformer including a primary winding connected to a power source and a secondary winding for output purposes;
switching means connected to said primary winding for controlling power supply to said primary winding;
an oscillator circuit for controlling on/off operation of said switching means;
abnormal condition detection means for developing a control signal for terminating oscillation operation of said oscillator circuit when an abnormal condition is detected;
said transformer further including an auxiliary winding for developing a voltage proportional to that developed th
rough said secondary winding, said voltage developed through said auxiliary winding being applied to said oscillator circuit for driving said oscillator circuit; said abnormal condition detection means including an overvoltage detection circuit connected to said auxiliary winding for developing said control signal when an overvoltage is developed through said auxiliary winding;
said overvoltage detection circuit including,
a reference voltage generation means for developing a reference voltage proportional to a voltage applied from said power source; and
comparing means for comparing said voltage developed through said auxiliary winding with said reference voltage in order to develop said control signal when said voltage developed through said auxiliary winding exceeds said reference voltage;
said oscillator circuit including an astable multivibrator, and a variable impedance means for varying an oscillation frequency of said astable multivibrator.
11. A power supply voltage stabilizer comprising:
transformer means including a primary winding connected to a power source, a secondary winding for producing an output voltage, and an auxiliary winding for developing a voltage proportional to said output voltage produced by said secondary winding;
switching means connected to said primary winding for controlling the power supply from said power source to said primary winding;
oscillator circuit means for controlling the on/off operation of said switching means;
overvoltage detection circuit means connected to said auxiliary winding for developing a control signal to terminate the oscillation operation of said oscillator circuit means when an overvoltage condition is detected, said overvoltage detection circuit means including,
means for developing a reference potential, and
12. A power supply voltage stabilizer comprising:
transformer means including a primary winding connected to a power source and having a voltage supplied thereto, a secondary winding for producing an output voltage, and an auxiliary winding for developing a voltage proportional to said output voltage produced by said secondary winding;
switching means connected to said primary winding for controlling the power supply from said power source to said primary winding;
oscillator circuit means for controlling the on/off operation of said switching means;
overcurrent detection circuit means connected to said primary winding for developing a control signal to terminate the oscillation operation of said oscillator circuit means when an overcurrent condition is detected, said overcurrent detection circuit means including,
means for monitoring said voltage supplied to said primary winding of said transformer means,
means for measuring the amount of current passing through said primary winding of said transformer means by translating said amount of current into a corresponding amount of voltage potential,
switching means responsive to said corresponding amount of voltage potential for switching to a first switched condition when the corresponding voltage potential exceeds a predetermined voltage potential and for switching to a second switched condition when said voltage potential does not exceed said predetermined voltage potential, and
comparing means responsive to said voltage supplied to said primary winding and connected to an output of said switching means for generating said control signal to terminate oscillation operation of said oscillator circuit means when said switching means switches to said first switched condition in response to the exceeding of said predetermined voltage potential by said corresponding voltage potential.
13. A power supply voltage stabilizer in accordance with claim 11 or 12 wherein said comparing means comprises a double base diode.
Description:
BACKGROUND AND SUMMARY OF THE INVENTION
The present invention relates to a power supply voltage stabilizer and, more particularly, to a power supply voltage stabilizer employing a switching system for controlling power supply to a transformer included in the power supply voltage stabilizer.
In the conventional power supply voltage stabilizer employing a switching system for controlling power supply to a transformer included in the power supply voltage stabilizer, there is a possibility that an abnormal overvoltagewill be developed from an output terminal thereof and/or an abnormal overcurrent may flow through the primary winding of the transformer.
Accordingly, an object of the present invention is to provide a protection means for protecting the power supply voltage stabilizer from an abnormal overvoltage and/or overcurrent.
Another object of the present invention is to provide a detection means for detecting an impending overvoltage and/or overcurrent occurring within the power supply voltage stabilizer.
Other objects and further scope of applicability of the present invention will become apparent from the detailed description given hereinafter. It should be understood, however, that the detailed description and specific examples, while indicating preferred embodiments of the invention, are given by way of illustration only, since various changes and modifications within the spirit and scope of the invention will become apparent to those skilled in the art from this detailed description.
The
power supply voltage stabilizer of the present invention mainly comprises a transformer including a primary winding connected to a commercial power source through a rectifying circuit, a secondary winding for output purposes, and an auxiliary winding. A driver circuit including a switching means is connected to the primary winding for controlling the power supply to the primary winding. An oscillator circuit is associated with the switching means to control ON/OFF operation of the switching means, thereby controlling the power supply to the primary winding.
To achieve the above objects, pursuant to an embodiment of the present invention, an overvoltage detection circuit is connected to the auxiliary winding. The overvoltage detection circuit functions to compare a voltage created in the auxiliary winding with the rectified power supply voltage, and develop a control signal, when an impending overvoltage is detected, for terminating operation of the oscillator circuit, thereby precluding power supply to the primary winding.
In another embodiment of the present invention, an overcurrent detection circuit is provided for detecting an impending overcurrent flowing through the primary winding to develop a control signal for terminating operation of the oscillator circuit.
BRIEF DESCRIPTION OF THE DRAWINGS
The present invention will become more fully understood from the detailed description given hereinbelow and the accompanying drawings, which are given by way of illustration only, and thus are not limitative of the present invention and wherein:
FIG. 1 is a circuit diagram of a basic construction of a power supply voltage stabilizer of the present invention;
FIG. 2 is a block diagram of an embodiment of a power supply voltage stabilizer of the present invention, which includes an oscillator circuit and an over voltage detection circuit;
FIG. 3 is a circuit diagram of an embodiment of the overvoltage detection circuit included in the power supply voltage stabilizer of FIG. 2;
FIG. 4 is a circuit diagram of an embodiment of the oscillator circuit included in the power supply voltage stabilizer of FIG. 2;
FIG. 5 is a waveform chart for explaining operation of the oscillator circuit of FIG. 4;
FIG. 6 is a block diagram of another embodiment of a power supply voltage stabilizer of the present invention, which includes an oscillator circuit and an overcurrent detection circuit; and
FIG. 7 is a circuit diagram of an embodiment of the overcurrent detection circuit included in the power supply voltage stabilizer of FIG. 6.
DESCRIPTION OF THE PREFERRED EMBODIMENTS
R
eferring now in detail to the drawings, and to facilitate a more complete understanding of the present invention, a basic construction of a power supply voltage stabilizer of the present invention will be first described with reference to FIG. 1.
The power supply voltage stabillizer mainly comprises a transformer T including a primary winding N 1 connected to a commercial power source V, a secondary winding N 2 connected to an output terminal V 0 , and an auxiliary winding N 3 . An oscillator circuit OSC is associated with the primary winding N 1 and the auxiliary winding N 3 to control the power supply from the commercial power source V to the primary winding N 1 .
A rectifying circuit E is connected to the commercial power source V for applying a rectified voltage to a capacitor C 1 . A negative terminal of the capacitor C 1 is grounded, and a positive terminal of the capacitor C 1 is connected to the collector electrode of a switching transistor Q 5 through the primary winding N 1 of the transformer T. The oscillator circuit OSC performs the oscillating operation when receiving a predetermined voltage, and develops a control signal toward the base electrode of the switching transistor Q 5 to control the switching operation of the switching transistor Q 5 . The switching transistor Q 5 functions to control the power supply to the primary winding N 1 , thereby controlling the power transfer to the secondary winding N 2 and the auxiliary winding N 3 .
The auxiliary winding N 3 is connected to a capacitor C 3 in a parallel fashion via a diode D 1 . A positive terminal of the capacitor C 3 is connected to the oscillator circuit OSC to supply a drive voltage Vc 3 . A negative terminal of the capacitor C 3 is connected to the emitter electrode of the switching transistor Q 5 and grounded. The positive terminal of the capacitor C 3 is connected to the primary winding N 1 via a diode D 2 and a capacitor C 2 in order to stabilize the initial condition of the oscillator circuit OSC.
The secondary winding N 2 functions to develop a predetermined voltage through the output terminal V 0 . A smoothing capacitor C 0 is connected to the secondary winding N 2 via a diode D 0 , and a series circuit of a resistor R 0 and a light emitting diode D i is connected to the smoothing capacitor C 0 in a parallel fashion. The light emitted from the light emitting diode D i is applied to a photo transistor Q 8 employed in the oscillator circuit OSC. The light emitting diode D i and the photo transistor Q 8 are preferably incorporated in a single package as a photo coupler.
The light amount emitted from the light emitting diode D i is proportional to the output voltage developed from the output terminal V 0 . The photo transistor Q 8 exhibits the impedance corresponding to the applied light amount. The oscillator circuit OSC is so constructed that the oscillation frequency is varied in response to variation of the impedance of the photo transistor Q 8 . Accordingly, the ON/OFF operation of the switching transistor Q 5 is controlled in response to the output voltage level, thereby stabilizing the output voltage level.
In the above constructed power supply voltage stabilizer, there is a possibility that an abnormal overvoltage is developed through the secondary winding N 2 and the auxiliary winding N 3 when the oscillator circuit OSC or the light emitting diode D i is placed in the fault condition.
FIG. 2 show
s an embodiment of the power supply voltage stabilizer of the present invention, which includes means for precluding occurrence of the above-mentioned overvoltage. Like elements corresponding to those of FIG. 1 are indicated by like numerals.
The power supply voltage stabilizer of FIG. 2 mainly comprises the transformer T, the oscillator circuit OSC, a driver circuit 1 including the switching transistor Q 5 , and an overvoltage detection circuit 3.
The positive terminal of the capacitor C 3 is connected to the driver circuit 1 and the oscillator circuit OSC to apply the driving voltage thereto. The positive terminal of the capacitor C 3 is also connected to the primary winding N 1 through the diode D 2 and a parallel circuit of the capacitor C 2 and a resistor R 2 in order to stabilize the initial start operation of the oscillator circuit OSC. The secondary winding N 2 is connected to an output level detector 2, which comprises the light emitting diode D i as shown in FIG. 1. The ON/OFF control of the switching transistor Q 5 is similar to that is achieved in the power supply voltage stabilizer of FIG. 1.
The secondary winding N 2 and the auxiliary winding N 3 are wound in the same polarity fashion and, therefore, the voltage generated through the auxiliary winding N 3 is proportional to that voltage generated through the secondary winding N 2 . The overvoltage detection circuit 3 is connected to receive the voltage at a point a as a power source voltage, and the voltage at a point b which is connected to the positive terminal of the capacitor C 3 . When the voltage level at the point b exceeds a reference level, the overvoltage detection circuit 3 develops a control signal for terminating the operation of the oscillator circuit OSC.
FIG. 3 shows a typical construction of the overvoltage detection circuit 3.
The voltage at the point a is applied to a series circuit of resistors R 3 and R 4 , and grounded. The voltage at the point b is applied to the connection point of the resistors R 3 and R 4 via a diode D 3 . The connection point of the resistors R 3 and R 4 is grounded through resistors R 5 and R 6 and a Zener diode Z 1 . A double-base diode (Trade Name Programmable Unijunction Transistor) P 1 is provided for developing the control signal to be applied to the oscillator circuit OSC. The anode electrode of the programmable unijunction transistor P 1 is connected to the connection point of the resistors R 3 and R 4 , the gate electrode of the programmable unijunction transistor P 1 is connected to the connection point of the resistors R 5 and R 6 , and the cathode electrode is connected to the oscillator circuit OSC.
When the voltage level of the point b exceeds a reference level VZ 1 , the programmable unijunction transistor P 1 is turned on to develop the control signal for terminating the oscillation operation of the oscillator OSC. In this way, the impending abnormal overvoltage is detected to protect the circuit elements. The ON condition of the programmable unijunction transistor P 1 is maintained as long as the main power switch is closed, because the overvoltage detection circuit 3 is connected to receive the voltage from the point a.
The voltage detection circuit 3 does not necessarily employ the programmable unijunction transistor. Another element showing the latching characteristics such as a negative resistance element can be employed instead of the programmable unijunction transistor.
FIG. 4 shows a typical construction of the oscillator circuit OSC.
The oscillation circuit OSC mainly comprises an astable multivibrator including transistors Q 1 , Q 2 and Q 3 , and an o
utput stage including a transistor Q 4 . The astable multivibrator is connected to receive the voltage appearing across the capacitor C 3 , and develops an output signal of which frequency is determined by the circuit condition as long as the multivibrator receives a voltage greater than a predetermined level.
The output signal of the output stage is applied to the base electrode of the switching transistor Q 5 included in the driver circuit 1 in order to switch the switching transistor Q 5 with a predetermined frequency. A transistor Q 9 is interposed between the base electrode of the transistor Q 3 and the grounded terminal. The transistor Q 9 is controlled by the control signal derived from the overvoltage detection circuit 3. Accordingly, the transistor Q 3 is turned off to terminate the oscillation operation when the abnormal overvoltage is detected by the overvoltage detection circuit 3.
Now assume that a voltage Vc 3 is developed across the capacitor C 3 . When main power supply switch is closed, the voltage Vc 3 varies in a manner shown by a curve X in FIG. 5. When the voltage Vc 3 reaches a predetermined level, the astable multivibrator begins the oscillation operation. More specifically, the transistor Q 1 is first turned on because the base electrode of the transistor Q 1 is connected to a capacitor C 4 of which the capacitance value is relatively small. At this moment, the transistor Q 2 is held off.
Because of turning on of the transistor Q 1 , the capacitor C 4 is gradually charged through a resistor R 4 and the transistor Q 1 . Accordingly, the base electrode voltage of the transistor Q 1 is gradually increased and, hence, the emitter electrode voltage of the transistor Q 1 is also increased to turn on the transistor Q 2 . When the transistor Q 2 is turned on, the transistor Q 3 is also turned on. The base electrode voltage of the transistor Q 2 which is bypassed by a resistor R 1 is reduced and, therefore, the transistor Q 2 is stably on. At this moment, the transistor Q 1 is turned off.
When the transistor Q 3 is turned on, the transistor Q 4 is turned on to develop a signal to turn on the switching transistor Q 5 . Upon turning on of the transistor Q 3 , the charge stored in the capacitor C 4 is gradually discharged through paths shown by arrows in FIG. 4. Therefore, the base electrode voltage of the transistor Q 1 is gradually reduced. When the base electrode voltage of the transistor Q 1 becomes less than a predetermined level, the transistor Q 1 is turned on, and the transistor Q 2 , Q 3 and Q 4 are turned off. Accordingly, the transistor Q 5 is turned off. After passing the initial start condition, the driving voltage Vc 3 is held at a predetermined level as shown by a curve Y in FIG. 5 to maintain the above-mentioned oscillation operation.
The photo transistor Q 8 is disposed in the discharge path of the capacitor C 4 in order to control the discharge period in response to the impedance of the photo transistor Q 8 . That is, the oscillation frequency is controlled in response to the light amount emitted from the light emitting diode included in the output level detector 2.
FIG. 6 shows another em
bodiment of the power supply voltage stabilizer of the present invention, which includes means for precluding occurrence of an abnormal overcurrent. Like elements corresponding to those of FIG. 2 are indicated by like numerals.
In the power supply voltage stabilizer of FIG. 1, there is a possibility that an abnormally large current flows through the primary winding N 1 when the magnetic flux is saturated due to requirement of large current at the secondary winding side. The power supply voltage stabilizer of FIG. 6 includes an overcurrent detection circuit 4 for detecting an impending abnormally large current.
A resistor R 9 is interposed between the emitter electrode of the switching transistor Q 5 included in the driver circuit 1 and the grounded terminal. The overcurrent detection circuit 4 is connected to receive a signal from the connection point of the resistor R 9 and the emitter electrode of the switching transistor Q 5 , thereby developing a control signal for terminating the oscillation operation of the oscillation circuit OSC.
FIG. 7 shows a typical construction of the overcurrent detection circuit 4.
The voltage at the point a is applied to a series circuit of resistors R 10 and R 11 , and grounded. The collector electrode of a transistor Q 10 is connected to the connection point of the resistors R 10 and R 11 through resistors R 12 and R 13 . The emitter electrode of the transistor Q 10 is grounded. The base electrode of the transistor Q 10 is connected to the connection point of the resistor R 9 and the emitter electrode of the switching transistor Q 5 via a resistor R 14 .
When the switching transistor Q 5 is turned on, a current flows through the resistor R 9 . When the voltage drop across the resistor R 9 exceeds a predetermined value due to a large current, the transistor Q 10 is turned on to turn on the programmable unijunction transistor P 1 . That is, when a large current flows through the primary winding N 1 , the programmable unijunction transistor P 1 develops the control signal to terminate the oscillation operation of the oscillator circuit OSC.
The invention being thus described, it will be obvious that the same may be varied in many ways. Such variations are not to be regarded as a departure from the spirit and scope of the invention, and all such modifications are intended to be included within the scope of the following claims.
The present invention relates to a power supply voltage stabilizer and, more particularly, to a power supply voltage stabilizer employing a switching system for controlling power supply to a transformer included in the power supply voltage stabilizer.
In the conventional power supply voltage stabilizer employing a switching system for controlling power supply to a transformer included in the power supply voltage stabilizer, there is a possibility that an abnormal overvoltage
will be developed from an output terminal thereof and/or an abnormal overcurrent may flow through the primary winding of the transformer. Accordingly, an object of the present invention is to provide a protection means for protecting the power supply voltage stabilizer from an abnormal overvoltage and/or overcurrent.
Another object of the present invention is to provide a detection means for detecting an impending overvoltage and/or overcurrent occurring within the power supply voltage stabilizer.
Other objects and further scope of applicability of the present invention will become apparent from the detailed description given hereinafter. It should be understood, however, that the detailed description and specific examples, while indicating preferred embodiments of the invention, are given by way of illustration only, since various changes and modifications within the spirit and scope of the invention will become apparent to those skilled in the art from this detailed description.
The
power supply voltage stabilizer of the present invention mainly comprises a transformer including a primary winding connected to a commercial power source through a rectifying circuit, a secondary winding for output purposes, and an auxiliary winding. A driver circuit including a switching means is connected to the primary winding for controlling the power supply to the primary winding. An oscillator circuit is associated with the switching means to control ON/OFF operation of the switching means, thereby controlling the power supply to the primary winding. To achieve the above objects, pursuant to an embodiment of the present invention, an overvoltage detection circuit is connected to the auxiliary winding. The overvoltage detection circuit functions to compare a voltage created in the auxiliary winding with the rectified power supply voltage, and develop a control signal, when an impending overvoltage is detected, for terminating operation of the oscillator circuit, thereby precluding power supply to the primary winding.
In another embodiment of the present invention, an overcurrent detection circuit is provided for detecting an impending overcurrent flowing through the primary winding to develop a control signal for terminating operation of the oscillator circuit.
BRIEF DESCRIPTION OF THE DRAWINGS
The present invention will become more fully understood from the detailed description given hereinbelow and the accompanying drawings, which are given by way of illustration only, and thus are not limitative of the present invention and wherein:
FIG. 1 is a circuit diagram of a basic construction of a power supply voltage stabilizer of the present invention;
FIG. 2 is a block diagram of an embodiment of a power supply voltage stabilizer of the present invention, which includes an oscillator circuit and an over voltage detection circuit;
FIG. 3 is a circuit diagram of an embodiment of the overvoltage detection circuit included in the power supply voltage stabilizer of FIG. 2;
FIG. 4 is a circuit diagram of an embodiment of the oscillator circuit included in the power supply voltage stabilizer of FIG. 2;
FIG. 5 is a waveform chart for explaining operation of the oscillator circuit of FIG. 4;
FIG. 6 is a block diagram of another embodiment of a power supply voltage stabilizer of the present invention, which includes an oscillator circuit and an overcurrent detection circuit; and
FIG. 7 is a circuit diagram of an embodiment of the overcurrent detection circuit included in the power supply voltage stabilizer of FIG. 6.
DESCRIPTION OF THE PREFERRED EMBODIMENTS
R
eferring now in detail to the drawings, and to facilitate a more complete understanding of the present invention, a basic construction of a power supply voltage stabilizer of the present invention will be first described with reference to FIG. 1. The power supply voltage stabillizer mainly comprises a transformer T including a primary winding N 1 connected to a commercial power source V, a secondary winding N 2 connected to an output terminal V 0 , and an auxiliary winding N 3 . An oscillator circuit OSC is associated with the primary winding N 1 and the auxiliary winding N 3 to control the power supply from the commercial power source V to the primary winding N 1 .
A rectifying circuit E is connected to the commercial power source V for applying a rectified voltage to a capacitor C 1 . A negative terminal of the capacitor C 1 is grounded, and a positive terminal of the capacitor C 1 is connected to the collector electrode of a switching transistor Q 5 through the primary winding N 1 of the transformer T. The oscillator circuit OSC performs the oscillating operation when receiving a predetermined voltage, and develops a control signal toward the base electrode of the switching transistor Q 5 to control the switching operation of the switching transistor Q 5 . The switching transistor Q 5 functions to control the power supply to the primary winding N 1 , thereby controlling the power transfer to the secondary winding N 2 and the auxiliary winding N 3 .
The auxiliary winding N 3 is connected to a capacitor C 3 in a parallel fashion via a diode D 1 . A positive terminal of the capacitor C 3 is connected to the oscillator circuit OSC to supply a drive voltage Vc 3 . A negative terminal of the capacitor C 3 is connected to the emitter electrode of the switching transistor Q 5 and grounded. The positive terminal of the capacitor C 3 is connected to the primary winding N 1 via a diode D 2 and a capacitor C 2 in order to stabilize the initial condition of the oscillator circuit OSC.
The secondary winding N 2 functions to develop a predetermined voltage through the output terminal V 0 . A smoothing capacitor C 0 is connected to the secondary winding N 2 via a diode D 0 , and a series circuit of a resistor R 0 and a light emitting diode D i is connected to the smoothing capacitor C 0 in a parallel fashion. The light emitted from the light emitting diode D i is applied to a photo transistor Q 8 employed in the oscillator circuit OSC. The light emitting diode D i and the photo transistor Q 8 are preferably incorporated in a single package as a photo coupler.
The light amount emitted from the light emitting diode D i is proportional to the output voltage developed from the output terminal V 0 . The photo transistor Q 8 exhibits the impedance corresponding to the applied light amount. The oscillator circuit OSC is so constructed that the oscillation frequency is varied in response to variation of the impedance of the photo transistor Q 8 . Accordingly, the ON/OFF operation of the switching transistor Q 5 is controlled in response to the output voltage level, thereby stabilizing the output voltage level.
In the above constructed power supply voltage stabilizer, there is a possibility that an abnormal overvoltage is developed through the secondary winding N 2 and the auxiliary winding N 3 when the oscillator circuit OSC or the light emitting diode D i is placed in the fault condition.
FIG. 2 show
s an embodiment of the power supply voltage stabilizer of the present invention, which includes means for precluding occurrence of the above-mentioned overvoltage. Like elements corresponding to those of FIG. 1 are indicated by like numerals. The power supply voltage stabilizer of FIG. 2 mainly comprises the transformer T, the oscillator circuit OSC, a driver circuit 1 including the switching transistor Q 5 , and an overvoltage detection circuit 3.
The positive terminal of the capacitor C 3 is connected to the driver circuit 1 and the oscillator circuit OSC to apply the driving voltage thereto. The positive terminal of the capacitor C 3 is also connected to the primary winding N 1 through the diode D 2 and a parallel circuit of the capacitor C 2 and a resistor R 2 in order to stabilize the initial start operation of the oscillator circuit OSC. The secondary winding N 2 is connected to an output level detector 2, which comprises the light emitting diode D i as shown in FIG. 1. The ON/OFF control of the switching transistor Q 5 is similar to that is achieved in the power supply voltage stabilizer of FIG. 1.
The secondary winding N 2 and the auxiliary winding N 3 are wound in the same polarity fashion and, therefore, the voltage generated through the auxiliary winding N 3 is proportional to that voltage generated through the secondary winding N 2 . The overvoltage detection circuit 3 is connected to receive the voltage at a point a as a power source voltage, and the voltage at a point b which is connected to the positive terminal of the capacitor C 3 . When the voltage level at the point b exceeds a reference level, the overvoltage detection circuit 3 develops a control signal for terminating the operation of the oscillator circuit OSC.
FIG. 3 shows a typical construction of the overvoltage detection circuit 3.
The voltage at the point a is applied to a series circuit of resistors R 3 and R 4 , and grounded. The voltage at the point b is applied to the connection point of the resistors R 3 and R 4 via a diode D 3 . The connection point of the resistors R 3 and R 4 is grounded through resistors R 5 and R 6 and a Zener diode Z 1 . A double-base diode (Trade Name Programmable Unijunction Transistor) P 1 is provided for developing the control signal to be applied to the oscillator circuit OSC. The anode electrode of the programmable unijunction transistor P 1 is connected to the connection point of the resistors R 3 and R 4 , the gate electrode of the programmable unijunction transistor P 1 is connected to the connection point of the resistors R 5 and R 6 , and the cathode electrode is connected to the oscillator circuit OSC.
When the voltage level of the point b exceeds a reference level VZ 1 , the programmable unijunction transistor P 1 is turned on to develop the control signal for terminating the oscillation operation of the oscillator OSC. In this way, the impending abnormal overvoltage is detected to protect the circuit elements. The ON condition of the programmable unijunction transistor P 1 is maintained as long as the main power switch is closed, because the overvoltage detection circuit 3 is connected to receive the voltage from the point a.
The voltage detection circuit 3 does not necessarily employ the programmable unijunction transistor. Another element showing the latching characteristics such as a negative resistance element can be employed instead of the programmable unijunction transistor.
FIG. 4 shows a typical construction of the oscillator circuit OSC.
The oscillation circuit OSC mainly comprises an astable multivibrator including transistors Q 1 , Q 2 and Q 3 , and an o
utput stage including a transistor Q 4 . The astable multivibrator is connected to receive the voltage appearing across the capacitor C 3 , and develops an output signal of which frequency is determined by the circuit condition as long as the multivibrator receives a voltage greater than a predetermined level. The output signal of the output stage is applied to the base electrode of the switching transistor Q 5 included in the driver circuit 1 in order to switch the switching transistor Q 5 with a predetermined frequency. A transistor Q 9 is interposed between the base electrode of the transistor Q 3 and the grounded terminal. The transistor Q 9 is controlled by the control signal derived from the overvoltage detection circuit 3. Accordingly, the transistor Q 3 is turned off to terminate the oscillation operation when the abnormal overvoltage is detected by the overvoltage detection circuit 3.
Now assume that a voltage Vc 3 is developed across the capacitor C 3 . When main power supply switch is closed, the voltage Vc 3 varies in a manner shown by a curve X in FIG. 5. When the voltage Vc 3 reaches a predetermined level, the astable multivibrator begins the oscillation operation. More specifically, the transistor Q 1 is first turned on because the base electrode of the transistor Q 1 is connected to a capacitor C 4 of which the capacitance value is relatively small. At this moment, the transistor Q 2 is held off.
Because of turning on of the transistor Q 1 , the capacitor C 4 is gradually charged through a resistor R 4 and the transistor Q 1 . Accordingly, the base electrode voltage of the transistor Q 1 is gradually increased and, hence, the emitter electrode voltage of the transistor Q 1 is also increased to turn on the transistor Q 2 . When the transistor Q 2 is turned on, the transistor Q 3 is also turned on. The base electrode voltage of the transistor Q 2 which is bypassed by a resistor R 1 is reduced and, therefore, the transistor Q 2 is stably on. At this moment, the transistor Q 1 is turned off.
When the transistor Q 3 is turned on, the transistor Q 4 is turned on to develop a signal to turn on the switching transistor Q 5 . Upon turning on of the transistor Q 3 , the charge stored in the capacitor C 4 is gradually discharged through paths shown by arrows in FIG. 4. Therefore, the base electrode voltage of the transistor Q 1 is gradually reduced. When the base electrode voltage of the transistor Q 1 becomes less than a predetermined level, the transistor Q 1 is turned on, and the transistor Q 2 , Q 3 and Q 4 are turned off. Accordingly, the transistor Q 5 is turned off. After passing the initial start condition, the driving voltage Vc 3 is held at a predetermined level as shown by a curve Y in FIG. 5 to maintain the above-mentioned oscillation operation.
The photo transistor Q 8 is disposed in the discharge path of the capacitor C 4 in order to control the discharge period in response to the impedance of the photo transistor Q 8 . That is, the oscillation frequency is controlled in response to the light amount emitted from the light emitting diode included in the output level detector 2.
FIG. 6 shows another em
bodiment of the power supply voltage stabilizer of the present invention, which includes means for precluding occurrence of an abnormal overcurrent. Like elements corresponding to those of FIG. 2 are indicated by like numerals. In the power supply voltage stabilizer of FIG. 1, there is a possibility that an abnormally large current flows through the primary winding N 1 when the magnetic flux is saturated due to requirement of large current at the secondary winding side. The power supply voltage stabilizer of FIG. 6 includes an overcurrent detection circuit 4 for detecting an impending abnormally large current.
A resistor R 9 is interposed between the emitter electrode of the switching transistor Q 5 included in the driver circuit 1 and the grounded terminal. The overcurrent detection circuit 4 is connected to receive a signal from the connection point of the resistor R 9 and the emitter electrode of the switching transistor Q 5 , thereby developing a control signal for terminating the oscillation operation of the oscillation circuit OSC.
FIG. 7 shows a typical construction of the overcurrent detection circuit 4.
The voltage at the point a is applied to a series circuit of resistors R 10 and R 11 , and grounded. The collector electrode of a transistor Q 10 is connected to the connection point of the resistors R 10 and R 11 through resistors R 12 and R 13 . The emitter electrode of the transistor Q 10 is grounded. The base electrode of the transistor Q 10 is connected to the connection point of the resistor R 9 and the emitter electrode of the switching transistor Q 5 via a resistor R 14 .
When the switching transistor Q 5 is turned on, a current flows through the resistor R 9 . When the voltage drop across the resistor R 9 exceeds a predetermined value due to a large current, the transistor Q 10 is turned on to turn on the programmable unijunction transistor P 1 . That is, when a large current flows through the primary winding N 1 , the programmable unijunction transistor P 1 develops the control signal to terminate the oscillation operation of the oscillator circuit OSC.
The invention being thus described, it will be obvious that the same may be varied in many ways. Such variations are not to be regarded as a departure from the spirit and scope of the invention, and all such modifications are intended to be included within the scope of the following claims.
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