PHILIPS 19TI500A/01 SANREMO CHASSIS PS101.08.0 3119 103 3022.0 INTERNAL VIEW.

The monocarrier chassis PS 101.08.0 3119 103 3022.0 is entirely based on tubes and very few semiconductors, mainly Germanium diodes, and was one of the first in such kind of technology in PHILIPS.

TUBES USED:

- PL500
- PY88
- DY87
- PCL85
- EF183
- PCF200
- PCL84
- PL84
- PCL86
- PCH200
- PCF802


PHILIPS 19TI500A /01 CHASSIS PS101.08.0 3119 103 3022.0 CIRCUIT ARRANGEMENT FOR PRODUCING A SAWTOOTH CURRENT ACROSS THE VERTICAL DEFLECTION COIL OF A TELEVISION RECEIVER, Philips Tubes vertical deflection


A circuit for introducing adjustable parabolic and S-components in a sawtooth current in a coil, wherein the coil is connected in the output of an amplifier device, con-sists of the series circuit of a charging capacitor, a wind-ing coupled to the coil, and a first resistor. A first series circuit of a second resistor and a reservoir capacitor is connected between the junction of the first resistor and winding and the junction of the winding and charging ca-pacitor, in that order. The junction of the second re-sistor and second capacitor are connected to the control electrode of the amplifier. The other end of the charging capacitor is connected to a variable tapping on a parallel resistance capacitance circuit in another input circuit of the device, in order to permit varying of the relative am-plitudes of the parabolic and S-components. A variable resistor is connected between the control electrode and the variable tapping in order to permit variation of the am-plitudes of the parabolic and S-component with respect to the sawtooth component.



The invention relates to a circuit arrangement for producing a sawtooth current across the vertical deflection coil of a television receiver. The coil is included in the output circuit of the vertical output stage, to the control-electrode of which is applied the sawtooth con-trol-signal which is developed across a charging capacitor included in the control-electrode circuit. The charging capacitor is periodically discharged and is recharged with the aid of a charging circuit which includes the se-ries combination of a resistor and a winding, lying outside the discharging circuit. The winding is magnetically cou-pled with a choke included in the output circuit of the 50 vertical output stage, through which winding a voltage is induced, which is opposite the capacitor voltage. Said winding has connected with it in parallel the series corn-bination of at least one resistor and one reservoir capaci-tor, the free end of the latter being connected to the June- 55 tion of the charging capacitor and the winding. A furher input electrode of the output stage has connected to it the parallel combination of a resistor and a capacitor. One end of a further resistor is connected to the control electrode of the vertical output stage, and the other end GO of the further resistor is coupled with the resistor con-nected to the said input electrode. Such a circuit arrangement is described in U.S. Patent No. 2,851,632. It is, however, necessary to add to each cycle of the sal,vtooth current one cycle of a parabola 65 component and also one cycle of a so-called &com-ponent. The parabola component is required in view of the fact that the vertical deflection coil is coupled through a trans-former with the vertical output stage. The same applies 70 to the case in which for other reasons than coupling through the transformer not only the vertical deflection
3,426,243 Patented Feb. 4, 1969
coil, behaving substantially like a resistor, but also an in-ductor is included in the output circuit of the vertical final stage.

The S-component is required in view of the fact that the display screen of the display tube in a television re-ceiver is flat. Therefore, the rate of deflection of the electron beam must be higher at the centre of the screen than at the edge in order to achieve a linear displacement of the spot on the display screen. The S indicates sym-bolically what form the current through the deflection coil must be for obtaining these desired deflection rates. Numerous circuit arrangements are known by which the desired current form can be produced. However, they have the disadvantage that they are either too compli-cated or are not capable of providing the correct ratio between the sawtooth, parabola and S-component. The circuit arrangement according to the invention is, on the contrary, simple and provides, in addition, the possibility of adjusting accurately the desired ratio between saw-tooth, parabola and S-component, while it prevents, in addition, an excessive influence of undesirable higher de-gree components in the produced current.
In order to produce the parabola and S-component, and permit adjustment of their amplitudes, the circuit arrangement according to the invention is characterized in that in parallel with the reservoir capacitor there is con-nected an integrating network which consists of the series combination of an integrating capacitor and an integrating resistor, the free end of the latter being coupled with the junction of the charging capacitor and of the reservoir capacitor. The junction of the integrating resistor and the integrating capacitor is connected to the control-electrode of the output stage. The end of the charging capacitor remote from the winding is connected to a variable tap-ping of the resistor connected to the input electrode. The impedance of the latter resistor is, in operation, great with respect to the impedance of the comparatively great parallel-connected capacitor. In addition, the further re-sistor is made variable, and the end thereof not connected to the control electrode is connected to the tapping of the resistor connected to the input electrode. Variation of the tapping point adjusts the relative ampltiudes of the parab-ola and S-component, while variation of the further resistor controls the relative amplitudes of the parabola and S-component with respect to the sawtooth. A few possible embodiments of circuit arrangements according to the invention will be described with reference to the accompanying figures, of which FIG. 1 shows a possible circuit diagram of an embodi-ment equipped with valves. FIG. 2 shows a partial substitute diagram of the ar-rangement of FIG. I. FIG. 3 shows a further diagrammatical substitute dia-gram of the arrangement of FIG. 2. FIG. 4 shows a first possible modification of the sub-stitute diagram of FIG. 3 and hence of the arrangement of FIG. I and FIG. 5 shows a second possible modification of the substitute diagram of FIG. 3 and hence also of the ar-rangement of FIG. 1. Referring to FIG. 1, the valve 1 is the vertical output stage of a television receiver, the anode circuit of which includes an output transformer 2. The vertical deflec-tion coil 4 is connected to the secondary winding 3 of said transformer 2. In order to produce the desired control-voltage for the control-electrode 5 o

f the valve 1, the grid circuit of said valve includes the following network. This net-work consists in the first place of a charging resistor 6, a winding 7 and a charging capacitor 8, which are connected in series with each other and the free end of the charging resistor 6 is connected to the positive supply voltage +VB. In practice the voltage +VB is usually derived from the horizontal output stage, since this stage is, in the first place stabilised and is, in addi-tion capable of providing a fairly high supply voltage, which is conducive to the linearity of the sawtooth volt-age to be produced. It will be seen from FIG. 1 that the end of the capacitor 8 remote from the winding 7 is connected, in accordance with a first principle of the invention, to a variable tapping 9 associated with a po-tentiometer 10, which is included in the cathode con-ductor of the valve 1. This resistor is shunted by a com-paratively large electrolytic capacitor 11, which is chosen so that its impedance is small for the repetition frequency of the sawtooth voltage to be produced with respect to the impedance of the resistor 10. As is in-dicated by the line 12 with the double arrow, the wind-ing 7 is magnetically coupled with the primary winding of the transformer 2. As is the case in said Patent No. 2,851,632 the sense of winding of the winding 7 is such that the sawtooth voltage 13 produced across the wind- 90 ing 7 is unlike the sawtooth voltage 14 produced across the capacitor 8. Also in this case this serves to ensure an optimum linearity of the sawtooth 14. The winding 7 has furthermore connected with it in parallel the series combination of a capacitor 15 and two resistors 16 and 17, the resistor 17 being variable. The network 15, 16 and 17 is provided for eliminating the peak developed across the winding 7 during the vertical fly-back from the signal 13, so that a signal 18 is finally produced across the capacitor 15, the polarity of this signal being opposite that of the voltage 14 across the capacitor 8, its waveform being, however, substantially identical to that of the latter. For this purpose the capacitor 15 must have a comparatively high value: a value of 68K pf. may be chosen and the resistors 16 and 17 serving as peak resistors must be comparatively small; values of 22K ohms and 10K ohms respectively may be chosen. According to a further aspect of the arrangement ac-cording to the invention the sawtooth voltage 18 is em-ployed for producing partly the required parabola com-ponent and partly the desired S-component. As will be explained more fully hereinafter, this means that fur-ther steps are required to ensure that the control-signal applied finally to the control-electrode 5 accurately con-tains the desired components with their correct ampli-tudes. In order to convert the sawtooth voltage 18 produced across the capacitor 15 into a signal containing the de-sired parabola and S-components, the capacitor 15 has connected with it in parallel the series combination of a capacitor 19, a resistor 20 and a large capacitor 21, operating as a blocking capacitor. The capacitor 21. is un-essential for the further explanation, it only serves to en-sure that the high direct voltage at the junction of the winding 7 and of the charging capacitor 8 cannot pene-trate to the control-grid S. Therefore, the network formed by the capacitor '19 and the resistor 20 constitutes the in-tegration network proper which has to ensure that the voltage V15 produced across the capacitor 15 is converted into a signal containing the desired correction corn-ponents. 'Finally, the third step according to the invention con-sists in that a resistor 22 is arranged between the con-trol-grid 5 and the variable tapping 9. In order to display that, in fact, the control-grid 5 has produced across it the desired control-signal and that by connecting the capacitor 8 and the resistor 22 to the variable tapping 9 the anode current starts passing through the valve 1, which contains all the desired com-ponents for providing accurately the correct waveform of the final current through the deflection coil 4, HG. 2 shows partially a substitute diagram of the arrange-rnent of FIG. 1. It will be apparent from FIG. 2 that the voltage Vg of capacitor 8 is indicated by at and the voltage V15 of capacitor 15 by in a and b are constants, which have each the dimension of a voltage per unit time. It will furthermore be obvious that, since finally the sawtooth voltage to be applied to the control-grid 5 must increase during the forward stroke, the number of turns of the winding 7 has to be chosen so that the amplitude of the signal 13, as far as the sawtooth por-tion is concerned, is smaller than the amplitude of the signal 14 and it follows therefrom that for the signal 18 V, ith respect to the signal 14 the same must apply. It therefore always applied a>b. For performing the desired calculation the circuit dia-gram of FIG. 2 is further simplified and shown in this form in FIG. 3. In .FIG. 3 the capacitor 15 is represent-ed by a voltage source 15', which supplies a voltage v15,. The capacitor 8 is represented by a source 8', which supplies the voltage Vg. The capacitor 21. is omit-ted from the diagram of FIG. 3, since it is large and un-essential for these explanations. It is furthermore as-sumed in the diagram of FIG. 3 that the source 15' pro-duces a current i1 through the network of the capacitor 19 and the resistor 20 only, whilst the sources 8' and 15' produce a current i2, which passes through the ca-pacitor 19 and resistor 22.

The greater the time constants R20C19 and R22C19 are 70 chosen, the small become the values of Pi and 132. Since, moreover, the denominator increases with an increas-ing degree in t (for t4 the denominator is 24 and for /3 it is already 120), the fourth and higher degree terms in Equation 5 can be neglected with respect to the first, 75 second and third degree terms with a correct choice of the resistors R20 and R22 and of the capacitor 19.

This signal contains, in principle, all the desired correction terms, since it contains not only the linear term, i.e. the sawtooth component (a—b)t but also the posi-tive quadratic term, i.e. the required parabolic component and a negative third-degree term, i.e. the component re-quired for the S-correction. This S- or third-degree com-ponent must, in fact, be negative, since with respect to 15 the flat display screen of the display tube the rate of scanning must be reduced both at the beginning and at the end of the stroke. This means a third-degree term must be subtracted from the linear term.

Since a>b, it follows therefrom that the positiveness of this coefficient depends upon the ratio between R20 and R22. On the basis of a positive term, it becomes constantly smaller according as R22 diminishes until it changes over from positive to negative, which means that by means of •R22 in a first instance the measure of parabolic correction and the measure of S-correction can be adjusted In principle, the desired extent of parabolic correction with respect to the sawtooth component could be adjusted, but this does not apply to the associated extent of S-cor-rection, since the terms pi and g2 occur in the parabolic component in the first power and in the S-component in the second power. Since the fl-values are small, the S-corn-ponent is smaller than the parabolic component. If the p values are raised, the S-component may be increased with respect to the parabolic component until the desired ratio between the parabolic and S-components is attained, after which without changing this ratio the two corn-ponents can be simultaneously decreased by varying R22 relatively to R20 to their desired values relative to the sawtooth component. By increasing the fl-values, how-ever, the negligence of the higher-power terms in Equa-tion 6 is no longer permissible. The control-signal will therefore contain not only the desired sawtooth, parabolic and S-components but also an excess of undesirable 4th, 5th and even higher power terms. This means that the increase in the values of g is re-stricted so that the desired ratio between the parabolic and S-components cannot be adjusted in this manner. According to the principle of the invention negative feedback is used apart from the introduction of the nega-tive sawtooth source V15= —bt and the parallel connec-tion therewith of the network R20r19, The anode current is of the valve 1 can be indicated by ia=S(Vi—aVic), wherein S is the mutual conductance of the valve 1, and VK is the cathode voltage thereof.

In the known circuit arrangements of Patent No. 2,851,632 the part of the arrangement for the production of the sawtooth and cor-rection voltages comprises four capacitors and five resis-tors. In the arrangement according to the invention five capacitors and six resistors are required. In principle, we are concerned with a different arrangement of a substan-tially equal number of parts, the values of which have to be chosen carefully or which have to be variable. In the foregoing the fact is left out of consideration that the voltage V15 obtained from the winding 7 contains not only a linear term —bt but also second- and third-degree components, since the anode current i a, which induces a voltage in the winding 7, contains second- and third-degree terms.
However, if the value of p, is chosen correctly, it can be said that the influence of the third- and fourth-degree terms in vo,tage V15 with respect to the linear term is negligible. An exact calculation can, of course, be made, in which all factors also the negative feedback through the winding 7 are considered. The formulae then obtained are, however, so compli-cated that it is difficult to make conclusions therefrom. In the explanation given above, it is therefore preferred to use an approximate calculation, which has the advantage of providing a good insight in the operation of the circuit arrangement. So far the function of the triode 23 has been left out of consideration, since it is not connected with the prin-ciple of the invention. This triode only serves for a periodi-cal discharge of the capacitor 8. To this end the signal derived from the output transformer 2 is applied through a further secondary winding 24 and various capacitors and resistors to the control-grid of the valve 23. The signal derived from the winding 24 has the same waveform as the signal 13 and ensures that during the fly-back the triode 23 gets into the conducting state, so that the capac-itor 8 is discharged. The terminals 24' and 25 receive frame synchronising pulses which provide a direct syn-chronisation of the valve 23. It appears therefrom that the oscillator circuit formed by the valves 1. and 23 is of the so-called trnultivibrator type, in which, however, the feed-back of the anode of the valve 1 to the control grid of the valve 23 is performed through the output transformer 2. It will be obvious, however, that any other control-method for valve 23 may be employed. The valve 23 may be formed by a blocking oscillator, so that this valve in itself is included in an independent oscillator circuit which provides a periodical discharge of the capacitor 8. The advantage of the arrangement of FIG. I is however, that a separate blocking transformer is economised, whilst only the winding 24 suffices for obtaining a self-oscillating circuit. It is neither strictly necessary for the deflection coil 4 to be connected through the winding 3 of the transformer 2 to the anode of the valve 1. When the impedance of the de-flection coil 4 allows so, it may be connected through a capacitor cutting off the direct current to the anode of the valve 1. In this case the primary winding of the trans-former 2 can be considered to be a choke with which the secondary winding 7 is magnetically coupled. The wind-ing 24 may, if desired, also be coupled with said choke, if a transformer arrangement of the multivibrator type is desired, or the winding 24 may be omitted, and the valve 23 may be formed by a blocking oscillator. Particularly, if transistors are used instead of valves, it is common practice to couple the vertical deflection coil 4 directly with the collector electrode of the output transistor.

It will be obvious that with the use of transistors all parts of the arrangement of FIG. I remain the same and that the operation is quite identical. In the calculations it is indifferent whether valves or transistors are employed. Possible modifications of the arrangement of FIG. I may be explained with reference to FIGS. 4 and S. FIG. 4 shows the resistor 22 connected, instead of being con-nected between the control-grid 5 and the tapping 9, to the earth-connected end of the resistor 10. This mode of connection brings about scarcely any difference with re-spect to the A.C. effect from that of FIG. 3, but with re-spect to the D.C. adjustment of the valve 1 there is some difference. In the case of FIG. 3 the D.C. bias voltage of the control-grid 5 will follow the displacement of the tapping 9. In the arrangement of FIG. 4 this is not the case. It will be obvious that this modification also holds good without the need for further means for the arrange-ment of FIG. I, since only the end of the resistor 22 re-mote from the control-grid 5 has to be connected to earth. A further possible modification is shown in FIG. 5. In parallel with the source 8' there is connected a poten-tiometer resistor 27, provided with a variable tapping 26. The end of the resistor 22 remote from the control-grid 5 is connected to the tapping 26. This modification operates accurately like that of FIG. 3, which may be explained as follows. It is assumed that the variable tapping 26 is dis-placed towards the connection with the variable tapping 9. Then the same arrangement is obtained as that of FIG. 3 and therefore the operation is therefore quite identical. If, however, the tapping 26 is displaced towards the junc-tion of the sources 8' and 15', the resistor 22 is in parallel with the resistor 20 and the operation of the arrangement of FIG. 5 will be accurately the same as that of FIG. 3, if resistor 22 had an infinite value. This means that in Equation 6 the factor 02=0 and that both the quadratic and S-components will assume maximum values. It will be seen that the displacement of the tapping 26 from the junction of the sources 8' and 15' towards the tapping 9 brings about an attenuation of the parabolic and of the S-components. It can therefore be said that the displace-ment of the tapping 26 in the said direction has the same effect as a decrease of the resistor 22 in the arrangement of FIG. 3. The modification of FIG. 5 may be realised in the ar-rangement of FIG. I by providing a potentiometer 27 with a tapping 26 in parallel with the capacitor 8 and by connecting the end of the resistor 22 remote from the control-grid 5 to the tapping 26. It should be noted that the resistance value of the potentiometer 27 should not be too high, since it should not effect too strongly the value of the factor p2• What is claimed is: 1. A circuit for producing a sawtooth waveform cur-rent in a coil, comprising: an amplifier device having an output electrode, and first and second input electrodes, output circuit means for coupling said output electrode to said coil, a charging capacitor, a discharging circuit connected to said charging capaci-tor for periodically discharging said charging capacitor, a
charging circuit for charging said charging capacitor and comprising a first series circuit connected in series with said charging capacitor, said first series circuit comprising a serially connected winding and first resistor means, means coupling said winding to said output circuit to provide a voltage across said winding opposing the charging capacitor voltage, a second series circuit of a first capacitor and second resistor means, means connecting said second series circuit in parallel with said winding, with one end of said first capacitor being connected to one end of said charging ca-pacitor, a third series circuit comprising a second capacitor and third resistor means connected in that order between the junction of said first capacitor and second resistor means and said one end of said charging capacitor, means connecting the junction of said second capacitor and third resistor means to said first input electrode, a parallel circuit comprising a third capacitor and fourth resistor means connected in parallel with said third capacitor, the impedance of said fourth resistor means being large with respect to the impedance of said third capacitor at the operating frequency, means connecting said parallel circuit between said sec-ond input electrode and a point of reference potential, and means connecting the other end of said charging capacitor to a tap on said fourth resistor means. 2. A circuit for producing a sawtooth waveform cur-rent in a coil, comprising: an electron discharge device having an anode, a cathode, and a control grid, output circuit means for coupling said coil to said anode, a source of potential having first and second terminals, a charging capacitor, 25 means connected to said charging capacitor for peri-odically discharging said charging capacitor, a charging circuit for said charging capacitor compris-ing a winding and first resistor means connected in that order between one end of said charging capacitor 30 and said second terminal, means coupling said winding to said output circuit to provide a voltage across said winding opposing the charging capacitor voltage, a first series circuit of a storage capacitor and second 35 resistor means connected in parallel with said winding with one end of said storage capacitor being con-nected to said one end of said charging capacitor, a second series circuit of an integrating capacitor and integrating resistor, means connecting said second series circuit in parallel with said storage capacitor, with one end of said integrating capacitor being connected to the other end of said storage capacitor, means connecting the other end of said integrating ca-pacitor to said control grid, a parallel circuit of potentiometer means and a capaci-tor connected in parallel with said potentiometer means, the impedance of said potentiometer means being large with respect to the impedance of said parallel capacitor at the operating frequency, means 'connecting said parallel circuit between said cathode and first terminal, and means connecting the other end of said charging capacitor to a tap on said potentiometer means. 3. The circuit of claim 2, in which said output circuit comprises a transformer having a primary winding con-nected to said anode and a secondary winding coupled to said coil, wherein said first-mentioned winding is a tertiary winding of said transformer. 4. The circuit of claim 2, comprising variable resistor means connected between said control grid and said tap. S. The circuit of claim 2, comprising variable resistor means connected between said control grid and said first terminal. 6. The circuit of claim 2, comprising a second potenti-ometer means connected in parallel with said charging capacitor, and resistor means connected between said con-trol grid and the tap on said second potentiometer means.

Deflection transformer system for television receivers (PHILIPS):

 The invention relates to a television receiver having a deflection transformer tuned by means of the leakage inductance to a harmonic of the flyback oscillation frequency and provided with an auxiliary winding in which an oscillation voltage is induced which substantially corresponds to the said harmonic. This latter oscillation may be used in a compensating circuit toobtain a flyback oscillation voltage (flyback pulse) from which the said harmonic is at least substantially removed.

A system utilizing such harmonic tuning is described in US. Patent No. 2,805,384, and is frequently used in particular to avoid interference oscillations and to obtain a high peak value of the high tension voltage at the secondary winding, but it involves the occurrence of a harmonic, usually the third harmonic, of the flyback pulse which, as is known, corresponds substantially to a sine half-wave. The present invention is an improvement over the system described in the aforesaid US. patent.

Since the harmonic has a considerable amplitude, the flyback pulse is markedly distorted. The harmonic is set up at the primary winding or another winding separated from the secondary so as to produce perceptible saddle distortion of the flyback pulse. This may be undesirable, especially if the flyback pulse is applied to a phase comparison stage for synchronizing the line deflection circuits. This shows itself particularly if differentiation is effected, i.e. from a truly sinusoidal half-wave a cosine half-wave is obtained having a substantially linear edge near the passage through zero. However, if a harmonic is present the differentiated curve has large amplitude' variations (humps) near the zero value, and may even change the sign of its slope. Such an altered edge isnot suited to ensure faultless operation in a phase discriminator.

To avoid this drawback a circuit arrangement of the kind referred to above has been proposed in which an additional winding is disposed in the leakage field of the high voltage secondary winding of a line deflection transformer and is connected between earth and the point at which the'pulse to be supplied to the phase comparison circuit is derived. This arrangement is based on the theory that an oscillation voltage substantially comprising harmonics only is set up in the additional winding. This harmnoic oscillation can be combined with the flybackoscillation, which is distorted by the same harmonic, in such a way that a pure flyback pulse from which the harmonic can be removed is supplied to the phase comparison circuit. However, in the arrangement proposed, the winding arranged in the leakage field is spaced from the core by a comparatively large distance and hence disposed at a point at which the leakage field is very weak. Consequently, a comparatively large and hence expensive coil is required to achieve the necessary amplitude of the compensating voltage. Furthermore, the coil has a comparatively low impedance, resulting in an inadmissible loading of the parallel connected winding of the deflection transformer so that the circuit arrangement will not always o erate satisfactorily. In addition, at the location of the additional winding, the leakage field is highly dependent upon circuit components arranged in the proximity, necessitating additional balancing to achieve satisfactory compensation.

In accordance with the invention, a television receiver is provided comprising a deflection transformer tuned by means of its leakage inductance to a harmonic of the flyback oscillation. The transformer is provided with an auxiliary winding in which an oscillation substantially corresponding to the harmonic is produced, enabling an oscillation to be obtained from which the harmonic is substantially removed. The above mentioned disadvantages are avoided and satisfactory compensation can be achieved whereby a pure flyback pulse is obtained by providing the additional winding upon the transformer core so that it substantially does not embrace the main magnetic flux. Thus the auxiliary winding has a ferro-magnetic core and hence a suitable impedance and may moreover be provided in a simple manner.

To obtain the flyback oscillation from which the harmonic is at least substantially removed, the auxiliary winding is advantageously connected in series with the primary of the transformer, or a part thereof. Thus, the desired satisfactory compensation of the harmonic from the flyback oscillation is achieved with very little additional loading effect.

In order that the invention may readily be carried into effect, an embodiment thereof will now be described, by way of example, with reference to the accompanying diagrammatic drawings, in which:

FIGURE 1 is a perspective view of a line deflection transformer of a television receiver, and

FIGURE 2 is the circuit diagram thereof.

Referring now to FIGURE 1, a ferrite core 2 constituted of substantially bar-shaped parts arranged so as to form a closed rectangle is secured to an angle support 1. The other end of the core 2 is supported by another angle support 3. The support 1 carries an insulating plate 4 on which are mounted soldering lugs 5 for the connections of the windings of the transformer.

A primary winding 7 is provided on the lower cross member of the ferrite core 2. In addition to its end terminals 2t winding 7 may have one or more tappings, not shown. The terminals and tappings of the Winding are connected to the soldering lugs 5 on the insulating plate 4. The winding 7 may comprise a number of discrete parts. On the upper cross member of the rectangular core is provided a high-voltage secondary 8 having aterminal 9 which may be connected with the aid of a cap 10 to the anode of a high voltage rectifier or the like, not shown.

As described in the aforesaid US. patent, in order to avoid interference oscillations in the deflection circuits of a television receiver, and to improve the high-voltage amplitude, the network comprising the windings 7 and 8 of the deflection transformer and the leakage inductance set up between them and the capacitances produced both in the primary and in the secondary are tuned to approximately 15 kc., which is the fundamental oscillation frequency of the flyback of the sawtooth current produced in the deflection device, and also approximately to the third harmonic thereof.

On the left-hand ends of the upper and lower cross members is provided an auxiliary winding 12 embracing the left-hand longer side of the rectangular core. The terminals of said winding are connected to soldering tags 13 and 14, respectively, mounted in an insulated manner on the support 3. As can be seen from FIG. 1, winding 12 comprises a first portion partially surrounding the lower horizontal leg of the transformer core and a second portion partially surrounding the upper horizontal leg of the transformer core. As will be evident, in each of these portions there are induced voltages having a fundamental frequency component and a harmonic frequency component. It will be evident from FIG. 1 that since the winding 12 is wound to include two opposite leg portions of the core, at any instant of time the main magnetic flux flowing in the ferrite core member 2 cuts the lower and upper portions of winding 12 in opposite directions thereby inducing approximately equal and opposite voltages in the ends of winding 12. Therefore, winding 12 can be considered to be the equivalent of two separate windings applied to the core in series opposition with the result that the fundamental frequency components of voltage induced in winding 12 by the main flux will be cancelled leaving only the harmonic frequency component of voltage at the output of the winding.

FIGURE 2 is a circuit diagram of the deflection transformer of FIGURE 1, similar reference characters relating to like parts. The primary winding 7 proper is preferably connected by means of input terminals 20 in the circuit of a controlled amplifying element, not shown, for example, a thermionic tube or a transistor having a control electrode to which a sawtooth voltage is supplied. The deflection coils may be connected to windings 7a and 7b coupled tightly to the primary winding 7. Between the winding 7 and the high-voltage secondary 8 there is a considerable leakage inductance by means of which the transformer is tuned in the above described manner to said harmonic of the flyback oscillation. One end of the high-voltage winding 8 is connected to the primary 7 and the other end to a cap 10 which may be mounted on a rectifier valve 19.

A fiyback pulse on which the harmonic is superimposed is set up in the windings 7a and 7b also. With the aid of the auxiliary winding 12 which embraces the stray flux, a voltage is induced therein which substantially corresponds to the harmonic only. A terminal 14 of the auxiliary winding 12 is connected by a lead 15 to one end of the winding 7b. The other end of winding 7b is connected to earth. If the number of turns of windings 12 and 7b are correctly chosen and the windings are connected so that the harmonic frequency components cancel one another, there is produced at a point 13 substantially complete compensation of the harmonic frequency so that through a lead 16 there may be applied to a deflector device 17 (FIGURE 1), or other suitable stage, a voltage (or a current) which substantially corresponds to the pure fundamental fiyback oscillation. The relative number of turns of windings 12 and 7b may be determined empirically. The oscillation may suitably pass in known manner from a terminal 16 through a differentiating network which may be mounted on the transformer, for example, on the plate 4 or the support 3.

The auxiliary winding 12 may alternatively be connected in series with another terminal of the windings 7a and 7b, for example, it may be connected between a tapping and earth. Thus compensation of the third harmonic is obtained at one winding and amplification at the other winding, and this may be desirable for many applications.

What is claimed is:

1. A circuit arrangement for generating deflection currents for a cathode ray tube device comprising a trace period of a first duration and a retrace period of a second duration, said arrangement comprising a transformer having a magnetic core for providing a main magnetic flux path, first and second winding means arranged on said core so as to provide a substantial leakage flux therebetween, said leakage flux imparting leakage inductance to said transformer, said first winding means comprising an input terminal adapted for connection to a source of deflection energy for supplying a periodically interrupted current flow in said first winding means whereby a fiyback pulse is induced therein having a fundamental oscillation frequency and a harmonic thereof, said transformer being tuned by means of said leakage inductance approximately to said harmonic of said fundamental oscillation frequency, an auxiliary Winding positioned on said core to link with a portion of said leakage flux and to be substantially free of any linkage with said main magnetic flux whereby a voltage is mduced therein of said harmonic frequency, and means for coupling said auxiliary winding to a portion of said first winding means so as to combine the voltages produced in said auxiliary winding and first winding means in a sense to produce a resultant voltage of said fundamental frequency wherein the harmonic frequency components of voltage are substantially cancelled.-

2. A circuit arrangement for generating deflection currents for a cathode ray tube device having a trace periodof a first duration and a retrace period of a second dura tion, said arrangement comprising a transformer having, a magnetic core, first and second winding means arranged on said core so as to provide a predetermined leakage flux therebetween, said leakage flux imparting leakage inductance to said transformer, said first Winding means comprising a first winding portion and a set? ond winding portion, input means for supplying a penodically interrupted current flow in said first winding portion whereby a fiyback oscillation pulse is induced in said first winding means having a fundamental frequency component and a harmonic frequency component, said transformer being tuned by means of said leakage inductance approximately to said harmonic frequency, an auxiliary winding mounted on said core in spaced apart relationship to said first and second Winding means so as to be in close mutual coupling relationship with said leakage flux and in loose coupling relationship with the main magnetic flux in said core whereby a Voltage of substantially said harmonic frequency only is induced in said auxiliary winding, and means for combining the voltages produced in said auxiliary winding and said second winding portion in a sense such that a resultant voltage is produced in which said harmonic frequency com ponents of voltage are substantially cancelled.

3. Apparatus as described in claim 2 wherein said harmonic frequency voltage is approximately the third harmonic of said retrace period frequency.

4. A television deflection circuit comprising a trans former, said transformer comprising a rectangular shaped magnetic core member providing a main magnetic flux path, first and second winding means arranged on said core so as to provide a substantial leakage flux therebetween, said leakage flux imparting leakage inductance to said transformer, said first winding means winding having a first winding portion adapted for connection to a source of deflection energy and a second winding portion adapted for connection to a deflection winding said deflection source being arranged to supply a periodically interrupted current flow in said first winding means having a fiyback period, said first winding means having a voltage induced therein during said fiyback period having frequency components comprising a predetermined fiyback oscillation frequency and a harmonic thereof, an auxiliary winding wound around one leg of said core in a direction substantially parallel to the direction of main magnetic flux flowing therein, said auxiliary winding being energized by said leakage flux and having an oscillation voltage induced therein of substantially said harmonic frequency, and means for coupling said auxiliary winding to the second winding portion of said first Winding means so as to combine the voltages induced in said second winding portion and said auxiliary winding in a sense to produce a resultant voltage substantially free of said harmonic frequency component.

5. Apparatus as described in claim 4 wherein said core member comprises first and second parallel legs and third and fourth legs perpendicular to said first and second legs, said first and second winding portions being wound about said core member in close mutual coupling rela;

tionship, said first winding portion being wound about said first leg of said core member and said second winding means being wound about said second leg of said core member, said auxiliary winding being Wound in the lengthwise direction about said third leg of said core member, said auxiliary winding being connected in series opposition with said second winding portion thereby to provide a resultant voltage substantially free of said harmonic frequency component.

6. A television deflection circuit comprising a transformer having a magnetic core providing a path for the main magnetic flux of said transformer, a primary winding, a secondary winding and a high voltage winding provided on said core, said windings being arranged on said core to provide a leakage flux which imparts .a leakage inductance to said transformer, said primary winding and said secondary winding being in close mutual coupling relationship, input means for supplying a periodically interrupted current flow in said primary winding having a flyback period, said primary and secondary windings each having a voltage induced therein having frequency components comprising a fundamental flyback oscillation frequency and a harmonic frequency thereof, said transformer being tuned by means of said leakage inductance approximately to said harmonic of the flyback oscillation frequency, an auxiliary winding wound on said core so as to embrace said leakage flux and in relatively loose mutual magnetic coupling relationship with said main magnetic flux whereby an oscillation voltage is induced therein of said harmonic frequency and which is substantially devoid of said fundamental flyback oscillation frequency, and means for connecting said auxiliary winding in series opposition with said secondary winding thereby to provide a resultant voltage substantially free of said harmonic frequency component.

7. Apparatus as described in claim 6 wherein said auxiliary winding is connected between a tap on said secondary winding and a point of reference potential and in a sense whereby the induced harmonic frequency component of voltage in said auxiliary winding opposes the harmonic frequency component of voltage induced in one portion of said secondary winding and aids the harmonic frequency component of voltage induced in a second portion of said secondary winding, and first and second output terminals connected to said first and second portions of said secondary winding, respectively, to supply first and second resultant voltages thereat having a minimum harmonic frequency component and a maxinum harmonic frequency component, respectively.

8. A circuit arrangement for generating deflection currents for a cathode ray tube device comprising a transformer having a magnetic core defining a main flux path, first and second winding means arranged on said core so as to provide a substantial leakage flux therebetween, said leakage flux imparting leakage inductance to said transformer, said first winding means having an input section and an output section, input means for supplying a periodically interrupted current flow in said first winding means having a flyback period, said first winding means having a flyback voltage induced therein during said flyback period having frequency components comprising a fundamental flyback oscillation frequency and a harmonic frequency thereof, said transformer being tuned by means of said leakage inductance approximately to said harmonic of the flyback oscillation frequency produced in said windings during said flyback period, means for correcting distortion in the flyback voltage produced comprising an auxiliary winding mounted on said core so that the voltage induced in a portion of said winding due to the main core flux of the fundamental flyback oscillation frequency substantially cancels a similar induced voltage in another portion of said auxiliary winding whereas the voltages of said harmonic frequency induced in each of said portions of the auxiliary winding energized by said leakage flux are additive, whereby the total induced voltage in said auxiliary winding is substantially free of said fundamental flyback oscillation frequency, and means for connecting said auxiliary winding in series opposition with a part of the output section of said first winding means whereby the harmonic frequency components of voltage substantially cancel each other.

9. Apparatus for producing a sawtooth deflection current in a cathode ray tube deflection coil, said apparatus comprising a transformer having a core of magnetic material defining a main magnetic flux path, winding means provided on said core and comprising a first winding portion and a second winding portion, said transformer having a leakage inductance determined by the leakage flux occurring between the windings of said transformer, input means coupled to said first winding portion for supplying a periodically interrupted current flow thereto whereby a flyback pulse is induced therein having a given fundamental flyback oscillation frequency and a harmonic frequency thereof, said transformer being tuned by means of said leakage inductance approximately to said harmonic frequency, an auxiliary winding wound on said core so as to comprise first and second effective winding portions, each of said first and second effective winding portions having induced therein a voltage having a component at said fundamental oscillation frequency and a component at said harmonic frequency, said first and second winding portions being effectively connected in series opposition so that said fundamental frequency components cancel one another thereby to produce a voltage across said auxiliary winding substantially of said harmonic frequency only, and means for coupling said auxiliary winding with said second winding portion of said winding means to produce a resultant output voltage wherein the harmonic frequency components of the voltages produced in said windings are substantially cancelled.

10. Apparatus for producing a sawtooth deflection current having a flyback period for a cathode ray tube system, said apparatus comprising a transformer having a magnetic core composed of a plurality of legs defining a main magnetic flux path, first and second winding means wound on different legs of said core so as to provide a leakage flux which imparts a leakage inductance to said trnasformer, said first winding means compirsing a first winding portion and a second winding portion, input means coupled to said first winding portion for supplying a periodically interrupted current flow in said first winding portion whereby a flyback pulse is induced in said first and second Winding means having a component of a given fundamental flyback oscillation frequency and a component of a harmonic frequency thereof, said transformer being tuned by means of said leakage inductance approximately to said harmonic frequency, an auxiliary winding wound on still another leg of said core in loose magnetic coupling relationship with said primary and secondary windings, said auxiliary winding being positioned on said core so that a voltage of substantially Zero net fundamental frequency component is induced therein and wherein the harmonic frequency components are additive to produce a net induced voltage of substantially said harmonic frequency component, and means for connecting said auxiliary winding in series opposition with said second winding portion to produce a resultant voltage of said fundamental frequency having a minimum harmonic frequency component.

11. Apparatus for producing a sawtooth deflection current having a flyback period for a cathode ray tube system, said apparatus comprising a transformer having a magnetic core, first and second winding means wound on said core so as to provide a leakage flux which imparts a leakage inductance to said transformer, said first winding means comprising a first winding portion and a second winding portion having a tap which divides said second winding portion into third and fourth winding portions, first and second output terminals connected to said third and fourth winding portions, respectively, input means coupled to said first winding portion for supplying a periodically interrupted current flow in said first winding portion whereby a flyback pulse is induced in said first and second winding means having a component of a given fundamental fiyback oscillation frequency and a component of a harmonic frequency thereof, said transformer being tuned by means of said leakage inductance approximately to said harmonic frequency, an auxiliary winding having first and second terminals and Wound on said core in loose magnetic coupling relationship with said first and second winding means, said auxiliary winding being positioned on said core so that a voltage of substantially zero net fundamental frequency component is induced therein and wherein the harmonic frequency components are additive to produce a net induced voltage of substantially said harmonic frequency component, means connecting said auxiliary Winding first terminal to said tap on said second winding portion thereby to provide a net voltage between said auxiliary winding second terminal and said first output terminal in which said harmonic frequency components are substantially cancelled and a net voltage between said auxiliary winding second terminal and said second output terminal in which said harmonic frequency components are additive.

12. Apparatus for producing a sawtooth deflection current in a cathode ray tube deflection coil, said apparatus comprising a transformer having a core of magnetic material, winding means provided on said core and comprising a first winding portion and a second winding portion, said transformer having a leakage inductance determined by the leakage flux occurring between the windings of said transformer, input means coupled to said first Winding portion for supplying a periodically interrupted current flow in said winding means whereby a flyback pulse is induced therein having a given fundamental fiyback oscillation frequency and a harmonic frequency thereof, said transformer being tuned by means of said leakage inductance to said harmonic frequency,

an auxiliary winding wound on said core so as to comprise first and second effective winding portions, each of said first and second effective Winding portions having induced therein a voltage having a component at said fundamental oscillation frequency and a component at said harmonic frequency, said first and second winding portions being effectively connected in series opposition so that said fundamental frequency components cancel one another thereby to produce a voltage across said auxiliary winding substantially of said harmonic frequency only, and means connecting said auxiliary winding in series with said second winding portion in a sense to produce a resultant voltage across the series combination thereof in which the harmonic frequency components are additive.



Tuning is obtained with rotatable drum selectors for VHF and variable rotatable capacitor for UHF.
A rotatable drum containing twelve pre-defined channel-specific filters determines the received channel, where the inductors of the input matching, the channel filter and the LO tank circuit are changed. The tuner is divided into two chambers for maximum isolation between the sensitive RF input and the mixer-oscillator-IF section with its much larger signals. Also on the drum there are eventually two separate sub-modules.
It's completely based on tubes technology.
With this concept, which essentially turned the tuner module into a kind of Lego building block construction, many different tuners became possible. Depending upon the country of destination and its associated standard and IF settings, the required filter modules would be selected. Service workshops and tv fabricants could later even add or exchange modules when new channels were introduced, since every inductor module had its individual factory code and could be ordered separately. As a consequence more versions of the tuner were produced, covering at least standards B, B-for-Italy, C. E, F and M.


The principle of the drum tuner. On an axis two times 12 regularly spaced channel-specific filter modules are mounted. In front are twelve channel filter modules for both the channel filter and LO tank circuit tuning. Seven contacts are available, and one module is shown removed. The second row contains 12 modules with five contacts for the input filter circuit. In the tuner module the front section (for mixer-ocillator and channel filter) is separated by a metal shield from the rear RF input and pre-amp section. [Philips Service "Documentatie voor de kanalenkiezers met spoelenwals", 1954]

Examples of the filter modules as used in the drum tuner. Left the 5-contact input filter, right the 7-contact BPF and LO tank filters. In both modules the coils are co-axial for (maximum) mutual coupling.





The second new valve introduced in the tuners family was the PCF80, a triode-pentode combo valve specifically designed for the VHF mixer-oscillator role. First order the circuit principles didn't change too much from the previous ECC81 based generation, with the triode acting as a Colpitts oscillator with a tuned feedback from anode to grid. The oscillator voltage was minimally 5V at the grid, and would be inductively coupled to the input of the mixer pentode. This inductive coupling was achieved by putting the oscillator coil S7 and the BPF coils S5 and S6 on the same rod inside the drum tuner filter modules, see Fig.5 above. By adjusting the distance between these coils for each channel filter module, the coupling constant could be kept more or less constant across all channels, providing as much as possible a frequency-independent mixer performance. For the mixer the pentode replaced the previous triode, providing more feedback isolation between anode and grid. All in all the new tuner must have given a considerable performance improvement compared to the previous generation.

Constant potential transformer / Constant Voltage transformer :

 The old B/W Tubes Television set was powered with a External Voltage stabiliser / Constant Voltage transformer unit (portable metal box) because  There was intermittent significant rapid line voltage dips here and there that were rather annoying when watching a tube set with an unregulated power supply (like all tvs of ancient times) and it eliminates the line dip issue completely.

(The, of mine, Pictured Constant Voltage transformer unit taken as example is a "KURTIS" STV/3 Italian Manufactured in Milan (Italy) in Year 1954 with a 250 VA power displacement and developed under Italian Patent 50499. It's clearly reported that input may be universal within -20%  +10% variations, output is precisely regulated within 1% range.........................click on pictures to enlarge them at full screen......)

The invention relates to voltage regulators of the type employed to supply alternating current and a constant voltage to a load circuit from a source in which the line voltage varies. They are particularly advantageous in connection with commercial applications such as amplifiers for talking motion pictures, amplifiers for radio transmitters,  Television sets (tubes),   mercury arc lamps, X-ray apparatus, etc.







 
Features : Instantaneous Voltage regulation. No effect of input Transient and spikes on the output. Sinusoidal output waveform. Was a  perfect answer and remedy for all types of electronic equipment. The  CVT have been designed to give you total protection against power related problems and to condition the power to suit the needs of Tubes television sets based equipment. It effectively regulates voltage variation, suppresses transients and bridges short interruptions/dips.

Basics: Ferro Resonant type Constant Voltage Transformers - CVT, the AC mains power the input winding, which The input winding normally runs at very moderate Flux linkage levels. The output winding exhibits an intrinsic energy characteristic and this energy storage operate in conjunction with mains capacitor to produce self-generated AC flux Field which is indirectly extracted from the Input Winding.
These Constant Voltage transformer or CVT use a tank circuit composed of a high-voltage resonant winding and a capacitor to produce a nearly constant average output with a varying input. The ferroresonant approach is attractive due to its lack of active components, relying on the square loop saturation characteristics of the tank circuit to absorb variations in average input voltage.

The ferroresonant action is a flux limiter rather than a voltage regulator, but with a fixed supply frequency it can maintain an almost constant average output voltage even as the input voltage varies widely.

All problems related to variation / fluctuation in Voltages are effectively handled because of this principle and a constant voltage output of ± 1% is given.

 INVENTOR: JOSEPH G. SOLA.

The  invention relates to an improved constant potential transformer by means of which variations of input voltage over a wide range of limits may take place without affecting the output voltage to any substantial extent.

One of the objects of my invention is to provide a constant potential transformer which is compact as a unit and which may be economically manufactured.

o1 It is another object of my invention to provide a transformer of this type in which the efficiency and input power factor are high while the temperature rise of the magnetic core is low.

A further object of my invention is to provide 1., a transformer, the outputvoltage wave of which will have very little distortion and the device will be satisfactory for various commercial applications.

The invention consists of the novel constructions, arrangments and devices to be hereinafter described and claimed for carrying out the above stated objects and such other objects as will appear from the following description of certain preferred embodiments illustrated in the accompanying drawings, wherein,Fig. 1 is a sectional view of one form of construction that may be used; Fig. 2 is a diagrammatic illustration of the wiring arrangement that may be used in connection with a construction such as that shown in Fig. 1; Fig. 3 is a sectional view of another form of construction embodying the principles of my invention; Fig. 4 is a diagrammatic illustration of the wiring arrangement that may be used in connection with a construction such as that shown in Fig. 3; Fig. 5 is a diagram showing the vector relations between the various voltages obtained in the illustrated constructions at different values of input voltage; and Fig. 6 is a graph showing the relation between the magnitudes of various voltages obtained in the illustrated constructions as the input voltage is varied.

Like characters of reference designate like parts in the several views.

Referring to Figs. 1 and 2, it will be seen that a core type of transformer construction is illustrated, the closed magnetic circuit 10 of which comprises a stack of I-shaped laminations II in abutting relation with the end legs 12a of a stack of E-shaped laminations 12, which may be held 5 together by any suitable means. On the end portion A of the core bar 11, I have provided a primary winding 13, the terminals 14 and 15 of which are adapted to be connected with a source of alternating current, the voltage of which from time to time may fluctuate or vary substantially. g On the end portion B of the core bar 11, I have mounted a winding 16, which is in spaced relation to but magnetically coupled with the winding 13, the winding 16 having terminal leads 17 and 18 and an intermediate tap 19. That part of the winding 16 between the lead I7 and tap 19 may be considered as an output or load winding, and the entire winding 16 between the leads 17 and 18 may be termed an intermediate winding.

The magnetic core 10 is provided with a high leakage reactance path between the windings 13 and 16 which in the form shown comprises the central leg 12b of the E-shaped laminations and which terminates short of the core bar 1 thereby providing a non-magnetic or air gap 20 between said leg 12b and the core bar II. In this arrangement, a condenser 21 is connected by leads 22 across the terminals 17 and 18 of the winding 16.
The lead 17 forms one side and the tap 19 the other side of what may be termed an output or load circuit. In the arrangement shown, an auxiliary winding 23 is positioned over the winding 13 and is magnetically coupled therewith, the terminals 24 of said winding 23 being connected in series in the lead 19 of said output circuit. In Figs. 3 and 4, I have illustrated my invention in connection with a well-known shell type of transformer having two closed magnetic circuits 10 and 10a comprising a straight central core bar 25 of I-shaped laminations, the sides of which are in abutting contact with the end legs 26a of the E-shaped laminations 26 and the end legs 27a of the E-shaped laminations 27, said parts being held in operative relation by any suitable means. On the end portion A, of the core bar 25, I have mounted a primary winding 28 the terminals 29 and 30 of which are adapted to be connected to a source of alternating current, the voltage of which may fluctuate substantially from time to time. Another winding 31 is positioned on the end portion B of the core bar 25, the winding 31 being in spaced relation to but magnetically coupled loosely with the winding 28.

A condenser 32 is connected across the terminals 33 and 34 of the winding 31. Another winding 80 35 is mounted on the end portion B of the core bar 25, in the arrangement shown the winding 35 being positioned over and magnetically coupled tightly with the winding 31. The terminal 36 of the winding 35 leads to one side of what may i be termed an output circuit. An auxiliary winding 37 is positioned on the end portion A of the core bar 25 and in the arrangement illustrated the winding 3I is positioned over and magnetically coupled tightly with the winding 28.

A lead 38 connects the winding.37 in series with the winding 35, the lead 39 of the winding 37 forming the other side of the aforesaid output circuit. The winding 35 may be termed an output or load winding and the winding 31 may be considered as an intermediate winding. The closed magnetic circuits described are each provided with a high leakage reactance path between the windings 28 and 37 on the end portion A of the core bar 25 and the windings 31 and 35 on the end portion B of said core bar, which in the arrangement shown comprise the central legs 40 and 41 of the respective E laminations 26 and 27. The shunts 40 and 41 terminate short of the adjacent sides of the core bar 25 thereby providing non-magnetic or air gaps 42 and 43 between the legs 40 and 41 and the core bar 25.

In Figs. 2, 4, 5 and 6 Vo represents the voltage across the output circuit, Vp shows the input voltage on the primary winding, Vs indicates the voltage derived from the winding 16 between the lead 17 and tap IS, and from the winding 35 forming parts of the respective output circuits, and Vpa is the component of the output voltage taken across the terminals of the auxiliary winding 23 or 31, as the case may be.
In Fig. 5, I have shown the vector relations of the various voltages in either arrangement at a certain power output and at different values of primary voltage. The various voltages are either not primed or are primed to correspond to the different values of Vp which is varied. As shown, Vpa is nearly 180* out of phase with Vs, and hence the vectorial sum Vo of the two is approximately their numerical difference.

In Fig. 6, I have illustrated graphically the relation in the constructions described between Vs, Vo, Vpa and Vp ata certain power output.

The principles upon which my improved transformer constructions operate will be clear from a detailed consideration of the construction shown in Figs. 3 and 4. The flux set up by applying a potential across the primary winding 28 will link with winding 31 and cause a definite reactance to be set up by that winding. As the voltage on the. primary winding is increased from zero to a higher level, the flux threading through winding 31 tends to increase in nearly direct proportion to the primary flux, due to the re5 luctance caused by the air gaps 42 and 43, a very slight amount leaking through the shunts 40 and 41. As the Induced E. M. F. reaches a higher value in winding 31 a critical point is reached where resonance takes place, since the reactance of the effective inductance of the winding 31 and the capacity reactance of the condenser 32 are approximately equal at the frequency of the voltage impressed on the winding 28. that is to say.

WCfL where f is the frequency of the voltage impressed on the primary winding 28, L is the effective 70 Inductance of the winding 31, and C is the capacity of the condenser 32. Under this resonant condition, a definite amount of current will flow in the resonant circuit, comprising the winding 31, condenser 32 and leads 33 and 34, and such t6 current will be limited by the constants of that circuit, with the result that a potential will be set up across the winding 31 and a corresponding amount of magnetic flux will be set up in the end portion B of the core bar 25.

It is well known that the inherent characteristic of a resonant circuit is such that its power vector may be many times greater than that of the generator which supplies the energy to the resonant circuit; in this case the energy is supplied by the primary of the transformer to the resonant circuit comprising winding 31 and condenser 32. By varying the primary voltage across winding 28 so that the magnetic density of section A thereof will still remain under the maximum magnetic density of section B of the core, with which the resonant circuit is associated, the change of flux density in section A of the core due to line variation in the primary will have no appreciable effect on the resonant circuit as the reluctance of the leakage path will be under that of section B of the core and flux will leak through the leakage path between the primary and resonant core portions, which leakage path comprises the shunts 40 and 41 and their respective nonmagnetic gap portions 42 and 43. It is due to this leakage reactance path also that the co-efficient of coupling between the primary winding 28 and the aforesaid resonant circuit is reduced to a certain optimum value, thereby maintaining a balanced condition so that the resonant circuit will continue to oscillate with the maximum current therein at a frequency equal to the frequency impressed on the primary winding. Under this state of resonance, winding 31 will set up a magnetic field in the core portion B which will remain practically constant so long as the density in the magnetic field of the core portion A remains at a lower density than that of the core portion B. It follows that this substantially constant field strength in core portion B will produce also a substantially constant voltage across the terminals of winding 31 and condenser 32, and this voltage will remain at practically a constant level regardless of variation of voltage applied to the primary winding 28. The aforesaid resonant circuit, therefore, becomes a constant primary source of voltage for any winding such as the winding 35 that is directly coupled to the winding 31. This coupling can be effected in any desired way, for example, by means of an auto-type transformer arrangement as shown in Fig. 2, or by mounting the winding 35 over the winding 31 as shown in Fig.

4. In the Fig. 4 construction, the output voltage of the windings 35 will also have a practically 5, constant level voltage independent of the voltage variation in the primary winding 28 so long as the circuit which includes the winding 31 remains in resonance.

The auxiliary regulating winding 37 is coupled go to the portion A of the core and is used to change the percentage of regulation of Vo across the terminals 36 and 39 of the output circuit with a variation of Vp. Since this auxiliary winding 37 on core portion A is directly coupled to the pri- 05 mary winding 28, the voltage induced will always be proportional to the turns ratio of primary winding 28 and the auxiliary winding 37.

A very constant level of voltage Vo across the terminals 36 and 39 may be obtained by suitably T0 apportioning the number of turns of said auxiliary winding 37 in relation to the number of turns in the winding 35. Any percentage of regulation of output voltage in relation to variations of Vp also may be obtained from terminals Ts 2 t ist. .y 36 and 39,-for example, an increase in the prinrary voltage on winding 28 will produce a decrease in output voltage Vo by properly arranging or apportioning winding 37 in relation to the winding 35.

The relation of voltages described has been upon the assumption that the transformer is on an open output circuit, that is to say, with no load on the terminals 36 and 39. If a load be applied on said terminals, a magnetic flux in the aforesaid resonant circuit will be developed corresponding to the load on said output circuit thereby unbalancing the magnetic flux in section B of the core. This density change in core section B will in turn affect the stable relation of the flux in core sections A and B and also the leakage reactance through the aforesaid shunt paths thereby causing a greater amount of useful flux from core section A to thread through core section B, which compensates for the energy used by the consuming circuit and at the same time maintains the resonant circuit in the desired oscillating condition.

It will be readily understood that in transformers embodying the principles of my invention the primary winding electrically connected to the source serves to induce voltage to the resonant circuit which is separated from the primary circuit by a high leakage reactance path, thereby providing a low co-efficient of coupling between the primary and the resonant circuits. The aforesaid resonant circuit may be considered as the primary or main source of controlling energy to the winding 35 and hence'to o3 the output or consuming circuit of the transformer.

My improved constant potential transformers are compact and efficient, and are of a small size relative to their power output as compared with other and more cumbersome and expensive apparatus intended for the same purpose. My improved transformers operate at an inherent high power factor, and the output voltage is very close to a pure sine wave.

My improved transformers may be used for many different purposes. They are particularly advantageous in connection with commercial applications such as amplifiers for talking motion pictures, amplifiers for radio transmitters,  Television sets (tubes),   mercury arc lamps, X-ray apparatus, etc.

I wish it to be understood that my invention is not to be limited to the specific constructions shown and described, except so far as the claims may be so limited, as it will be apparent to those skilled in the art that changes in the constructions and arrangements may be made without departing from the principles of my invention.

I claim:1. In a constant potential transformer, the combination of a magnetic core, a winding on said core adapted to be connected to a source of alternating current of fluctuating voltage, a second winding on said core, said core providing a high leakage reactance path for a portion of the flux to thread through one of the windings to the exclusion of the other winding, and means for maintaining the potential across the second winding substantially constant regardless of fluctuations in the input voltage comprising a resonant circuit including said second winding and a condenser, the resonant circuit operating at a frequency equal to the frequency of the voltage impressed on the first winding.
2. In a constant potential transformer, the 7T combination of a magnetic core, a winding on said core adapted to be connected to a source of alternating current of fluctuating voltage, a second winding on said core in spaced relation to said first winding, said core having magnetically disposed between said windings a magnetically 6 permeable shunt with a non-magnetic gap portion, and means for maintaining the potential across the second winding substantially constant regardless of fluctuations in the input voltage comprising a resonant circuit including said second winding and a condenser, the resonant circuit operating at a frequency equal to the frequency of the voltage impressed on the first winding.

3. In a constant potential transformer, the combination of a closed magnetic circuit comprising first and second core portions, a winding on said first core portion adapted to be connected to a source of alternating current of fluctuating voltage, a second winding on said second core portion, said circuit providing a high leakage reactance path for a portion of the flux to thread through one of the windings to the exclusion of the other winding, and means for maintaining the potential across the second winding substantially constant regardless of fluctuations in the input voltage comprising a resonant circuit including said second winding and a condenser, the resonant circuit operating at a frequency equal to the frequency of the voltage impressed on the first winding, the magnetic density at maximum predetermined input voltage of the first core portion being less than the maximum magnetic density of the second core portion.

4. In a constant potential transformer, the 85 combination of a closed magnetic circuit comprising first and second core portions, a winding on said first core portion adapted to be connected to a source of alternating current of fluctuating voltage, a second winding on said second core portion in spaced relation to said first winding, said circuit having magnetically disposed between said windings a magnetically permeable shunt with a non-magnetic gap portion, and means for maintaining the potential across the second winding substantially constant regardless of fluctuations in the input voltage comprising a resonant circuit including said second winding and a condenser, the resonant circuit operating at a frequency equal to the frequency of the voltage impressed on the first winding, the magnetic density at maximum predetermined input voltage of the first core portion being less than the maximum magnetic density of the second core portion.

5. A constant potential transformer comprising in combination a magnetic core, a primary winding on said core adapted to be connected to a source of alternating current of fluctuating voltage, a load winding on said core adapted to be connected to an output circuit, said core providing a high leakage reactance path for a portion of the flux to thread through one of the windings to the exclusion of the other winding, and means for maintaining the potential across the load winding substantially constant regard- 05 less of fluctuations in the input voltage comprising a resonant circuit including a condenser and a third winding, the resonant circuit operating at a frequency equal to the frequency of the voltage impressed on the primary winding, the third winding being in inductive relation to the load winding.

6. A constant potential transformer comprising in combination a magnetic core, a primary winding on said core adapted to be connected to a source of alternating current of fluctuating voltage, a load winding on said core in spaced relation to said primary winding and adapted to be connected to an input circuit, said core having magnetically disposed between said winlings a magnetically permeable shunt with a non-magnetic gap portion.; and means for maintaining the potential across the load winding substantially constant regardless of fluctuations in the input voltage comprising a resonant circuit including a condenser and a third winding, the resonant circuit operating at a frequency equal to the frequency of the voltage impressed on the primary winding, the third winding being in inductive relation to the load winding.

7. A constant potential transformer comprising in combination a closed magnetic circuit comprising first and second core portions, a primary winding on said first core portion adapted to be Sconnected to a source of alternating current of fluctuating voltage, a load winding on said second core portion and adapted to be connected to an output circuit, said magnetic circuit having magnetically disposed between said windings a magnetically permeable shunt with a non-magnetic gap portion, and means for maintaining the potential across the load winding substantially constant regardless of fluctuations in the input voltage comprising a resonant circuit including a conSdenser and a third winding, the resonant circuit operating at a frequency equal to the frequency of the voltage impressed upon the primary winding, the third winding being on the second core portion and in inductive relation to the load winding, the magnetic density at maximum predetermined input voltage of the first core portion being less than the maximum magnetic density of the second core portion.

8. A constant potential transformer comprising in combination a magnetic core, a primary wind40 ing on said core adapted to be connected to a source of alternating current of fluctuating voltage, a load winding on said core adapted to be connected to an output circuit, said core providing a high leakage reactance path for a portion of the 45 flux to thread through one of the windings to the exclusion of the other winding, a resonant circuit including a condenser and a third winding, the resonant circuit operating at a frequency equal to the frequency of the voltage impressed on the 50 primary winding, the third winding being in inductive relation to the load winding, and an auxiliary winding on the core in inductive relation to the primary winding and in series with the load winding, for the purpose described.
55 9. A constant potential transformer comprising in combination a closed magnetic core comprising first and second core portions, a primary winding on said first core portion adapted to be connected to a source of alternating current of fluctuating 60 voltage, a load winding on said second core portion and adapted to be connected to an output circuit, said core having magnetically disposed between said windings a magnetically permeable shunt with a non-magnetic gap portion, a reso65 nant circuit including a condenser and a third winding, the resonant circuit operating at a frequency equal to the frequency of the voltage impressed on the primary winding, the third winding being in inductive relation to the load winding, and an auxiliary winding on said first core portion in inductive relation to the primary winding and in series with the load winding, the magnetic density at maximum predetermined input voltage of said first core portion being less thain the maximum density of said second core portion.

10. A constant potential transformer comprising in combination a magnetic core, a primary winding on said core adapted to be connected to a source of alternating current of fluctuating voltage, a second winding on said core provided with two leads and an intermediate tap, one of said leads and said tap leading to an output circuit, said core providing a high leakage reactance path for a portion of the flux to thread through one of the windings to the exclusion of the other winding, and means for maintaining in said output circuit a substantially constant potential regardless of fluctuations in the input voltage cornprising a resonant circuit including a condenser connected in series between the leads of said second winding, the resonant circuit operating at a frequency equal to the frequency of the voltage impressed on the primary winding.
11. A constant potential transformer comprising in combination a magnetic core; a primary winding on said core adapted to be connected to a source of alternating current of fluctuating voltage; a second winding on said core provided with two leads and an intermediate tap; said core having magnetically disposed between said windings a magnetically permeable shunt with a non-magnetic gap portion; and means for maintaining in said output circuit a substantially constant potential comprising a resonant circuit ineluding a condenser connected in series between the leads of the second winding, the resonant circuit operating at a frequency equal to the frequency of the voltage impressed on the primary winding, and an auxiliary winding on said core in 40 inductive relation to the primary winding and in series with the load winding.
12. A constant potential transformer comprising in combination a closed magnetic core comprising first and second core portions; a primary 45 winding on said first core portion adapted to be connected to a source of alternating current of fluctuating voltage; a second winding on the second core portion and provided with two leads and an intermediate tap; one of said leadsandsaidtap 50 leading to an output circuit; said core having magnetically disposed between said windings a magnetically permeable shunt with a non-magnetic gap portion; the maximum density at maximum predetermined input voltage of said first 55 core portion being less than the maximum density of said second core portion; and means for maintaining in said output circuit a substantially constant potential comprising a resonant circuit including a condenser connected in series between 60 the leads of the second winding, the resonant circuit operating at a frequency equal to the frequency of the voltage impressed on the primary winding, and an auxiliary winding on said core in inductive relation to the primary winding and o5 in series with the load winding.

JOSEPH G. SOLA.

Transformer having constant and harmonic free output voltage

This invention relates to voltage transforming and regulating apparatus, and to core and coil constructions therefor, more particularly to such apparatus having a substantially harmonic free output voltage, and it is an object of the invention to provide improved apparatus and constructions of the character indicated.

It is a further object of the invention to provide improved apparatus of the character indicated having an output voltage which is substantially constant irrespective of variations of input voltage over a certain range, and which is substantially free of harmonics.

It is a further object of the invention to provide an improved transformer.

To provide a source of alternating current voltage of a desired frequency which is free of harmonics, that is, a sine wave, has long been a problem because of the undesired eifects produced thereby. For example, instruments which receive a voltage having harmonics therein may give erroneous and sometimes erratic indications. Apparatus supplied with a voltage having harmonies therein may overheat, and its useful life may be lessened. If the transformer which is supplying a voltage is responsible for the generation of harmonics, the supply transformer as well as the apparatus connected to it may overheat.

Commercial power systems supplying alternating current voltage approach the desired condition of a harmonic free voltage, and a large amount of technical eifort is devoted thereto. However, even with the extensive attention directed to this problem, it frequently occurs, in industrial areas particularly, that the supply voltage has an undesired percentage of harmonics.

In the Patent No. 2,143,745, Joseph G. Sola, entitled Constant Voltage Transformer, there is disclosed and claimed apparatus including a transformer and a condenser wherein a substantially constant output voltage is obtained throughout a certain range of variation in input voltage. While the output voltage of apparatus constructed according to the said patent has good wave form, that is, one largely free of harmonics, under certain conditions the voltage output has included as much as five per cent of third harmonic.

Filter circuits which are connected between the output of a source and a load and which serve to substantially reduce or eliminate harmonics are known. Such filters generally require the use of additional condensers and inductors and will correct the output voltage only when load current is flowing. Moreover, the correction may depend upon the amount of the load, there being the greatest correction at full load and substantially none at no load.

Accordingly, it is a further object of the invention to provide an improved transformer which will provide a constant output voltage substantially free of harmonics, which does not require additional condensers or inductors, and which will substantially eliminate the harmonics from no load to full load.

It is a further object of the invention to provide an improved transformer of the character indicated which will have improved efficiency in operation and which is economical to manufacture.

In carrying out the invention in one form, a transformer is provided having substantially constant output voltage and a substantially harmonic free output voltage and comprising in combination, a core, a primary winding and a secondary winding on the core, a high reluctance shunt magnetically disposed between the primary 2,694,177 Patented Nov. 9, 1954 and secondary windings, a third winding disposed on the core in a position to link with a portion of the leakage flux of the secondary winding and to be substantially free of any linkage with the leakage flux of the primary winding, a condenser which is connected in circuit with the secondary winding and the third winding, the condenser having a value of capacity such that when the transformer is excited with a voltage of predetermined magnitude and frequency a condition of a series resonant nature exists at that frequency, and means for connecting a load circuit to a certain portion of the secondary winding.

For a more complete understanding of the invention, relilferfince should be had to the accompanying drawings in w to Figure 1 is a sectional view of a transformer core and coils according to one form of the invention, and

Figure 2 is a diagrammatic representation of a system according to the invention and employing the core and coils of Fig. 1.

Referring to Figs. 1 and 2 of the drawing, the invention is shown embodied in regulating apparatus including a core and coil arrangement 10 having input, output, regulating and compensating windings and a condenser 11 connected to certain of these windings, all to be more particularly described.

The core and coil arrangement 10 comprises a core 12 which may be made of laminations stamped in the form shown and made of suitable material such, for example, as 26 gauge transformer C steel. The core, as shown, is composed of laminations or layers, each of which consists of two pieces, and when assembled into a stack of desired thickness form an outer piece or shell 13 and a center leg 14. The outer shell includes a pair of end legs 6 and 7 and a pair of side legs 8 and 9. The laminations of center leg 14 may be stamped from the pieces forming the outer shell 13 as part of the same process during which the openings or coil windows 15, 16, 17, 18, 19 and 21 are also formed. A core of the proper thickness is formed by assembling together the required number of outer shell laminations and pressing into the appropriate space the same number of center leg laminations assembled together, as is well understood in this art.

Each lamination of the outer shell 13, as shown, comprises a complete or continuous piece of metal with no joints therein. It will be understood, however, that the same configuration can be made up of individual pieces if so desired. Projecting inwardly from leg 8 between the coil windows 16 and 17 is a member 22 formed of the corresponding parts of the laminations of shell 13, and projecting inwardly from leg 9 between coil windows and 18 is a member 23 also formed of the corresponding parts of the laminations of shell 13. Projecting inwardly between coil windows 17 and 21 is a member 24 formed of parts of the laminations of shell 13, and projecting inwardly between coil windows 18 and 19 is a member 25 also formed of the corresponding parts of the laminations of shell 13. Projecting outwardly from the center leg 14 are members 26 and 27 formed of corresponding parts of the center leg laminations and so disposed as to lie between the coil windows 15 and 18 and 16 and 17 and to be disposed opposite the members 23 and 22, respectively, when the center leg 14 is disposed in shell 13 with the right end thereof forming the joint 28.

The members 22 and 27 are spaced from each other by a nonmagnetic gap 29, and the members 23 and 26 are spaced from each other by a nonmagnetic gap 31. The members 24 and 25 are formed of such a length as to tightly abut the center leg 14 at the joints 32 and 33 and have a cross-sectional area substantially less than that of the end leg 7 of the outer shell 13. The center .leg 14 is formed of a length so as to tightly abut the outer shell at joint 28 at one end and to leave a nonmagnetic gap 35 between the other end of the center leg and the inside surface of end leg 7.

Coil windows 15 and 16 comprise a space within which a primary winding 36 and a compensating winding 37 are disposed; coil windows 17 and 18 form a space within which a secondary winding 38 is disposed;

and coil windows 19 and 21 comprise a space within which a neutralizing winding 3% is disposed. Each of the coils or windings 36, 3'7, 38 and 39 comprise an appropriate number of turns and are provided with sufficient insulation, as is shown schematically in Fig. 1. Each of the coils may be preformed and placed upon the center leg and the unit pressed into the outer shell so as to form the nonmagnetic gap 35 and the abutting joints 23, 32 and 33.

The members 22 and 27 and gap 29, and members 23 and 26 and gap 31, form a high magnetic leakage path between the primary winding 36 and the secondary winding 38. The width of the members 22, 27, 23 and and the length of the nonmagnetic gaps 23 and 31 are chosen so as to provide the desired amount of magnetic leakage reactance, as will become clear subsequently in this specification. While the members 22 and 2'7 and gap 29, and members 23 and 26 and gap 31, as shown, form a high magnetic leakage pathway, it will be understood that the high magnetic leakage pathway may be formed in other well understood manners.

The members 24 and 25, the end of leg 14 together with the end leg 7 and the nonmagnetic gap 35 complete the end path for magnetic flux generated by the primary winding. Since the joints 32 and 33 are press-fits, there is little magnetic reluctance thereat, and consequently the members 24 and 25 form a return path which carries the major portion of the primary flux. These mom bers, however, are formed narrower than the end leg 7 whereby a small percentage of the primary flux flows through the end leg 7. The nonmagnetic gap 35 produces high reluctance in the path of the primary flux, thereby reducing the amount of flux which would flow through leg 7 if the gap were not there, and increasing the percentage of primary flux which flows through members 24 and 25.

The structure as thus far described in Fig. l is illustrated diagrammatically in Fig. 2, the same reference characters being used in the two figures to designate corresponding parts. Thus the windings 36 and 38 are disposed on a common core with a high leakage reactance shunt 22, 27, 29, 23, 26, and 31 disposed therebetween, winding 39 is disposed on the same magnetic core with the nonmagnetic gap 35 separating the core parts, and winding 3'7 is disposed in a closely coupled relationship to winding 36.

The effect of the high leakage path between primary winding 36 and secondary winding 38 is to relatively loosely couple these windings so that each of the windings has a high leakage reactance, and nonmagnetic gap 35 tends to isolate the winding 39 from the flux of the primary winding.

The primary winding 36 is adapted to be connected to a line or source by conductors 41 and 42. The secondary winding 38 has one of its ends connected by means of a conductor 43 to one terminal of condenser ll, and has its other end connected by means of a conductor 44 to one end of neutralizing winding 39 by a conductor 45. The other end of neutralizing winding 3% is connected by means of a conductor 46 to the other terminal of condenser 11. The conductors 44 and 45 connected together may be connected to one side of a load circuit through a conductor 47, and the other side of the load may be connected through a conductor 48 to one end of a compensating winding 37, the other end of which is connected by means of a conductor 49 to a tap on the secondary winding 38. The load circuit may then be traced as follows: From one side of the load through conductor 47, conductor 44, the right-hand portion of winding 38, conductor 49, winding 37, and conductor 43 to the other side of the load.

The operation of the apparatus may perhaps best be understood by considering its operation in two phases; that is, as a constant voltage apparatus alone, and as the combination of the constant voltage and the harmonic elimination or neutralizing apparatus. Considering first the constant potential aspects of the apparatus, it may be made such in one form by removing, in efiect, the neutralizing winding 39. Referring to Fig. 2, this may be accomplished by connecting conductor 46 to conductors 44 and 47 and disconnecting conductor 45 from conductors 44 and 47. When so connected, the apparatus of Figs. 1 and 2 is essentially similar to the form of the apparatus illustrated in the Patent No. 2,143,745, already hereinbefore referred to. When connected in this form as only a constant potential device,

the members 24 and 25, together with leg 7, form a portion of the return circuit for the primary winding flux and provide a return leg having substantially the same elfgctgive cross section as the other flux return legs 8 an For a complete understanding of the operation of the device in this form as a constant voltage transformer, reference may be had to the aforesaid Patent No. 2,143,745. Briefly, however, when voltage above a certain magnitude is applied to the primary winding 36 through conductors 41 and 42, a condition approximating series resonance is set up in the apparatus, and particularly in the circuit including condenser 11 and winding 38. When this condition exists, a substantially constant voltage is obtained across conductors 4'7 and 49 over a wide range of variations in voltage applied to the primary winding. Such small changes as occur in this voltage may be compensated for by the winding 37 which is closely coupled to winding 36 and which is in such a relation as to buck the voltage existing across conductors 47 and 49. Thus, if the primary voltage rises and the output voltage would tend to rise on account thereof, the compensating winding prevents it. Likewise, if the primary voltage falls and the output voltage tends to fall, the bucking voltage is also reduced and the output voltage remains the same. By proper choice of turns of winding 37, the load voltage, that is, the voltage appearing across conductors 47 and 48, is made substantially constant.

Vvhile explanation of the operation of this form of the device as a constant potential apparatus does not lend itself to simple terms, it is thought that the currents flowing in the condenser 11 and winding 38, due to the existing resonance condition, set up a llux condition in the portion of the core underneath and directly associated with the winding 38, due to the presence of the shunts between the primary and secondary windings 36 and 38, such that changes in flux caused by changes in voltage across the primary winding are largely absorbed in the shunts and thus do not change the flux conditions of the secondary winding. The output voltage or" the device as a constant voltage transformer has good wave shape, but it does have appreciable percentages of harmonies in it which are eliminated by the presence of the neutralizing winding 39. When the device is operating as a constant voltage apparatus and the winding 39 is present in the core but is not connected to the circuit, the winding 39 will, of course, have a voltage induced into it since a certain percentage of flux will course through the center leg 14 and through the end leg 7. With the core constructed as shown and described, it has been found that the voltage of coil 3? has a high percentage of odd harmonics in it, that is, third, fifth, seventh and ninth, etc. There is also present a certain value of fundamental since the winding 39 is linked by a small percentage of the flux set up by the primary winding. The presence of the odd harmonic voltages in winding 39 is due to the linkage of winding 39 by the leakage flux created by winding 38 when current flows through the condenser 11 and winding 33. This leakage flux, of course, has two pathways to follow, one of these including a portion of the central leg 14, the members 24 and 25, a portion of the legs 8 and 9 of the core,

. which links with winding 39, that is, that portion of these windings prior to such connection.

the secondary leakage flux which flows across gap 35 and through leg 7. The leakage flux of the primary winding 36 flows largely through the shunts 22, 27, 29 and 23, 26, 31 and thus does not link with winding 39. Consider now the second phase of the device. The winding 39 is connected in circuit with and in additive polarity to winding 38 and with condenser 11 as shown, to form a constant voltage and harmonic free device. When so connected the combined voltage of windings 38 and 39 is increased over the sum of the voltages of With the con nections so made, the percentage of odd harmonics existing in the winding 38 and across the conductors 47 and 49 is very much reduced and a constant voltage output also is had. They are, in fact, reduced to a virtually negligible amplitude. After. the connection has been made, as shown in Fig. 2, the harmonic voltage still '5 exists across winding 39 and also across the condenser 11, but these harmonic voltages are of such phase that they neutralize the harmonics which formerly existed in the Winding 38. For example the third harmonic, which exists in winding 39, is induced therein by the leakage flux from Winding 38, and this harmonic voltage is approximately 180 out of phase with the third harmonic voltage existing in winding 38.

With winding 39 connected into circuit in additive polarity, there has been, in effect, a number of turns added to the secondary winding, but these turns and the core configuration produce harmonic elimination and do not destroy the constant voltage. The flux in the core remains such that the condition of a series resonant nature still exists and hence substantially constant volt age exists across Winding 38. In order to have the proper value of output voltage with the higher voltage available when winding 39 is connected in circuit with winding 38 in additive polarity, the number of turns of winding 38 may be less than in a construction having only constant voltage output of the same value.

The number of turns in winding 39, the cross-sectional area of members 24 and 25, the length of gap 35, and the cross-sectional area of leg 7 enter into the magnitude of the third harmonic voltage produced as compared with the fundamental voltage in winding 39. The fundamental component is not essential since winding 38 may have a sufficicnt number of turns to produce the necessary value thereof, and it is thought that by coupling the winding 39 to the winding 38, as shown, the necessary .third harmonic neutralizing voltage is obtained while at the same time the fundamental voltage is not changed much.

Reduction of the harmonic voltages, and consequently currents in winding 38, reduces the heating of the windings and of the iron thereby making the transformer itself more eificient and economical, this being an advantage in addition to the desirable effects due to the lack of harmonics in loads.

By way of additional and more complete disclosure, one form of apparatus which was constructed and op; erated may be particularly described. This apparatus had a continuous rating of 500 volt amperes, a rated primary (across conductors 41 and 42) voltage range of 90 to 125 volts, a rated load voltage (across conductors 47 and 48) of 115 volts, and a rated load current of 4.35 amperes. In this apparatus the primary winding 36 had 106 turns of No. 13 copper wire arranged in 10 layers of 11 turns per layer, the winding 37 had 12 turns of No. 14 copper wire arranged in one layer of 12 turns, the secondary winding 38 had 405 turns of No. 15 copper wire arranged in 14 layers of 29 turns each, and the winding 39 had 207 turns of No. 15 copper wire arranged in 23 layers of 9 turns each. That portion of winding 38 lying between conductors 44 and 47, that is, the load portion of the winding, had 290 turns arranged in 10 layers.

The core of the apparatus described was designed to operate at a flux density of 100,000 lines per square inch and consisted of a stack of laminations 3 inches thick of No. 26 gauge transformer C steel. The length of side legs 8 and 9 was 6 inches and the length of end legs 6 and 7 was 5 inches; the width of end leg 6 and side legs 8 and 9 adjacent windings 36 and 38 was /8 of an inch; the width of side legs 8 and 9 adjacent winding 39 and the width of end leg 7 was /8 of an inch; the width of members 24 and 25 was A of an inch; the width of center leg 14 inside of coils 36 and 38 and members 24 and 25 was 1% inches, and the width of leg 14 inside of coil 39 was of an inch; the width of shunt members 22, 27, 23 and 26 was /2 of an inch; the length of gaps 29 and 31 was 0.050 of an inch; and the length of gap 35 was 0.150 of an inch. The width of center leg 14 inside of coil 39 may be the same as inside of coil 38 and the number of turns in coil 39 changed to fit the different space of windows 19 and 21.

The condenser 11 had a capacity of 16 microfarads and was rated at 660 volts.

By way of further disclosure, the results of a harmonic analvsis on the foregoing apparatus. as described and particularized, may be summarized. The first analysis was made at no load; that is, there'was no load connected across conductors 47 and 48. The winding 36 was connected to a sine wave generator supplying 115 volts R. M. S. A harmonic analysis of the sine wave generator voltage indicated that 'the voltage supplied to winding 36 had a fundamental component (60 cycles) of arbitrarily assigned amplitude equal to 100 per cent, and a third harmonic of 1.1 per cent of the fundamental, the remaining harmonics being less than one per cent of the fundamental and consequently negligible. With this same connection, the R. M. S. voltage across condenser 11, that is, across combined windings 38 and 39, was 610 volts. The harmonic analysis of this voltage showed on the basis of a fundamental of arbitrarily assigned amplitude equal to per cent, a third harmonic having an amplitude of 7 per cent, and a fifth harmonic having an amplitude of 2 per cent all in terms of the fundamental. The voltage across the winding 39 had an R. M. S. amplitude of 122 volts. The harmonic analysis showed on the basis of a fundamental of arbi trarily assigned amplitude equal to 100 per cent, a third harmonic having an amplitude of 100 per cent, a fifth harmonic having an amplitude of 20 per cent, a seventh harmonic having an amplitude of 4 per cent, and a ninth harmonic having an amplitude of 17 per cent, all in terms of the fundamental. The voltage across winding 38 had an R. M. S. amplitude of 522 volts, the harmonic analysis showing on the basis of a fundamental of arbitrarily assigned amplitude equal to 100 per cent, a third harmonic having an amplitude of 1.1 per cent, a seventh harmonic having an amplitude of l per cent, and a ninth harmonic having an amplitude of 1.8 per cent, all in terms of the fundamental. Correspondingly, the voltage across that portion of winding 38 between conductors 44 and 49 (load winding) had an R. M. S. amplitude of 127 volts, the harmonic analysis showing on the basis of a fundamental of arbitrarily assigned amplitude equal to 100 per cent, a third harmonic having an amplitude of .4 per cent, a fifth harmonic having an amplitude of .6 per cent, a seventh harmonic having an amplitude of 1.2 per cent, and a ninth harmonic having an amplitude of 1.6 per cent, all in terms of the fundamental. The output voltage, that is, the voltage across conductors 47 and 48, had an R. M. S. value of 114 volts with the harmonic analysis showing on the basis of an arbitrarily assigned fundamental component having an amplitude equal to 100 per cent, a third harmonic having an amplitude of .4 per cent, a fifth harmonic having an amplitude of .7 per cent, a seventh harmonic having an amplitude of 1.3 per cent, and a ninth harmonic having an amplitude of 1.7 per cent, all in terms of the fundamental.

The percentage of harmonics at the load conductors 47 and 48 is of the same general order as that of the applied voltage, the third harmonic being an improvement and some of the higher harmonics being very slightly increased.

In the apparatus as described and for the harmonic values given, when the conductor 46 was connected to the conductor 44, that is, the winding 39 was removed from the circuit as previously described, and the same sine wave generator was connected to the winding 36, the voltage across winding 36 had an R. M. S. amplitude of 115 volts. A harmonic analysis thereof showed on the basis of a 6D cycle or fundamental component arbitrarily assigned an amplitude of 100 per cent, a third harmonic having an amplitude of .8 per cent, a fifth harmonic having an amplitude of .4 per cent, and a seventh harmonic having an amplitude of .3 per cent, all in terms of the fundamental. The voltage across condenser 11 or across winding 38 had an R. M. S. amplitude of 467 volts, the harmonic analysis showing on the basis of a fundamental component of 100 per cent, a third harmonic having an amplitude of 23 per cent, and a fifth harmonic having an amplitude of 6 per cent, all in terms of the fundamental. The portion of winding 38 forming the load winding, that is, the winding connected across conductors 47 and 49, had an R. M. S. amplitude of 113 volts, the harmonic analysis showing on the basis of a fundamental component arbitrarily assigned an amplitude of 100 per cent, a third harmonic having an amplitude of 23 per cent, and a fifth harmonic having an amplitude of 6 per cent, all in terms of the fundamental. Under these conditions, the output voltage, that is, across conductors 47 and 48, had an R. M. S. amplitude of 100 volts, the harmonic analysis showing on the basis of a fundamental component arbitrarily assigned an amplitude of 100 per cent, a third harmonic having an amplitude of 27 per cent, a fifth harmonic having an amplitude of 7 per cent, and a seventh harmonic having an amplitude of one per cent, all in terms of the fundamental. The voltage across winding 39 had an R. M. S. amplitude of 73 volts, a harmonic analysis showing on he basis-of a fundamental componen arbitrarily assignedau amplitude f 100. per cent. a-third harmonic havin an amplitude of 11.00, per cent, a fifth harmoni havingan amplitudeof .78 per cent, a sev nth harmonic having an amplitude; of percent, an a ninth harmonic having an amplitude'of 6 per cenhall in terms of the fundamental.

A compari n f he rela ive harmonic val es across conductors a7 and 43 with the condenser c nnected to include the winding 39 andto exclude it, reveals. the reduction in the harmonic content' t? he output vol age.

A m lar h rmonic a alysis was. made with the apparatus opera ng at full loa with th sin wavesource as alr adyescrib providing l.15 volts acros he primary winding 36. With, the condenser 11 connected s shown in F gthe output volt ge across conductors 47 and cent, a third harmonic having an amplitude of 1-1 per cent, a fifth harmonic having an arriplittldev of .4 per cent, a seventh harmonic having an amplitude of 1.6 percent, an a ni th h rmonic having an amplitude of 1.2 p r. cent. These harmonic values are not substa tially diiferent from those taken at no load. Under the full load condition described, the voltage across winding 3,9had an R. M. S. amplitude of 111 volts, the harmonic analysis showing on the basis of a fundamental component arbitrarily assigned an ampltiude of 100 per cent, a third harmonic-having an amplitude of ,98 per cent, a fifthv harmonic having an amplitude of 16 per cent, a seventh harmonic having an amplitude of ll per cent, and a ninth harmonic having an amplitude of 11 per cent, all in terms of thefundamental- The vol age across Condenser 11 had an R. M. S. value of 593 volts with the harmonic analysisshowing n the basis of a fundamental component arbitrarily assigned an amplitude of 100 per cent, a third harmonic having an amplitude of 13 per cent, a fifth harmonic having an amplitude of 1.5 per cent, a seventh harmonic having an amplitude of .2 per cent, and a ninth harmonic having an amplitude of .1 per cent, all in terms of the fundamental. The voltage across winding 38'had an R. M. S. amplitude of 512 volts, the harmonic analysis show ing a fundamental component arbitrarily assigned an amplitude of 100 per cent, a third harmonichaving an amplitude of 1.7 per cent, a fifth harmonic having an amplitude of zero per cent, a seventh harmonic having an am.- plitude of 1.4 per cent, and a ninth harmonic having an amplitude of 1.2 per cent.

With full load being supplied by the transformer, and i with the condenser 11 connected so as to-remove wind.- ing .39 from the circuit,-tha.t is, conductor connected to conductor 44, the output voltage across conductors 4.7. and 48 had an R. M. S. amplitude of '97 volts, the harmonic analysis showing on the basis of a fundamental component arbitrarily assigned an amplitude of 10.0 per cent, a third harmonic having an amplitude of 23 per cent, a fifth harmonic having an amplitude of 6 per cent, and a seventh harmonic haying'an amplitude of .Tper cent. The voltage of winding 3.8 or condenser 11 had an, R. M. ,S. amplitude of 452 volts, the harmonic analysis showing a fundamental component arbitrarily assigned an amplitude of .100 per cent, a third harmonic having an amplitude of '20 per cent, a fifth harmonic having ah amplitude of per cent, and a seventh harmonichaving an amplitude of ,4 per cent. Comparing the relativeharlmonic value between the-full load condition where-in the neutralizing winding 39 is connected into and out .of the circuit, reveals that the harmonic content is very much by the presence of winding 39 in the core structure defined.

The loads fed by the transformer in the preceding tests were resistance loads.

"The structure as shown in Fig. 2 and having the harmonic analysis as given, was connected to a re ular The. in en on ha ing h s be descr ed, Wha is el imedandde re to. be s cur d by L e s. a nt s:

A transformer having substantially costant output voltage and a substantially armonic free voltage comprising, a core, a primary winding and a secondary winding on said core, ahigh reluctance shunt magnetrc l v disposed t eens d v nd ngs, a con e av ng a value of capacity such that when'connected across said secondary winding and the transformer is excited with a voltage of predetermined magnitude and frequency a condition of a seriesresonaut nature exists at the said freq v, a third ind ng d pos d n sa d ore n a P tion to link with a portion ofthe leakage flux of said secondary Windingand to be substantially free of any linkage with the leakage flux of said primary winding, said secondary winding, said third winding and said condenser being connected in circuit, and means for connecting a load circuit to at least a certain portion of said secondary winding.

2. A transformer having substantially constant output voltage and a substantially harmonic free output voltage comprising, a core, a primary winding and a secondary winding on said core, a high reluctance shunt magnetically disposed between said windings, a condenser having a value of capacity such that when connected across said secondary winding and the transformer is excited with a voltage of predetermined magnitude and frequency a condition of a series resonant nature exists at the said frequency, a third winding disposed on said core in a positionto link with a portion of the leakage flux of said secondary windingand to be substantially free of any linkage with the leakage flux of said primary winding, said secondary winding, said third winding and said condenser being connected in circuit with said third winding in additive polarity to said secondary winding, a compensating winding disposed on said core in close coupled relationship with said primary winding and connected in b ng r lat onship to saidse ary nd ng. and means for connecting a load circuit to at least a certain portion of said secondary winding and to said compensating winding,

A ns m ha ing suhstantia yc nst toutput voltage and a substantially harmonic free output voltage comprising, a core, a primary winding and a secondary winding on said core, a high reluctance shunt magnetically disposed-between said windings, a condenser having a value of capacity such that when connected across said secondary winding and the transformer is excited with a voltage of predetermined magnitude and frequency a condition-of a series resonant nature exists at the said frequency, a harmonic eliminating winding disposed on said core in a position to link with a portion of the leakage flux'of said secondary winding and to be substantially free of any linkage with the leakage flux of said primary winding, said secondary winding, said harmonic eliminating winding and said condenser being connected in circuit, and means for connecting a load circuit to at least a certain portion of said secondary winding.

4. A transformer having substantially constant output voltage and a substantially harmonic free output voltage comprising, a core, a primary winding and a secondary winding on said core, a high reluctance shunt magnetically disposed between said windings, a condenser having a value of capacity such that when connected across said secondarywinding and the transformer is excited with a voltage of predetermined magnitude and frequency a condition of a series resonant nature exists at the-said frequency, a third w'mding disposed on said core in a position to link with a portion of the leakage flux of said secondary winding and to be substantially free of any linkage with the leakage flux of said primary winding, saidse'condary winding, saidthird winding and said condenser being connected in a series circuit with said third winding in additive polarity relative to said secondary winding, and means for connecting a load circuit to at least a certain portion .of said secondary winding.

5- A n o m h in subs ant ally con tant ou pu voltage an a substanti l y harmonic free output lt ge mpr sing, a c e, a pr ary Winding and a se nd ry in g o said co e, a hi h re uct n s un ma c ly d posed be ween a d i di s, .a cond se having a alu o apac y such t a h n e ted a r ss sai se da y in ing. and he t an former is excited with a voltage of predetermined magnitude and frequency a condition of a series resonant nature exists at the said frequency, a thir:l winding disposed on said core, the leakage flux path of said third winding including a portion having low reluctance and a portion having high reluctance to the fluxes of said primary and secondary windings, said secondary winding, said third winding and said condenser being connected in circuit, and means for connecting a load circuit to at least a certain portion of said secondary winding.

6. A transformer having substantially constant output voltage and a substantially harmonic free output voltage comprising, a core, a primary winding and a secondary winding on said core, a high reluctance shunt magnetically disposed between said windings, a condenser having a value of capacity such that when connected across said secondary winding and the transformer is excited with a voltage of predetermined magnitude and frequency a condition of a series resonant nature exists at the said frequency, a third winding on said core, a low reluctance shunt magnetically disposed between said third winding and said primary and secondary windings, and high reluctance means disposed in the flux path of said third winding, said secondary winding, said third winding and said condenser being connected in circuit, and means for connecting a load circuit to at least a certain portion of said secondary winding.

7. A transformer having substantially constant output voltage and a substantially harmonic free output voltage comprising, a core, a primary winding disposed on one leg of said core, a secondary winding disposed on said one leg, said primary and secondary windings being relatively loosely coupled thereby to provide said windings with high leakage reactance, a condenser having a value of capacity such that when connected across said secondary winding and the transformer is excited with a voltage of predetermined magnitude and frequency a condition of a series resonant nature exists at the said frequency, a third winding on said one leg, at low reluctance shunt disposed between said third winding and said secondary winding, high reluctance means in said core beyond said shunt, and means for connecting a load circuit to at least a certain portion of said secondary winding.

8. A transformer having substantially constant output voltage and a substantially harmonic free output voltage comprising, a core, a primary winding disposed on one leg of said core, a secondary winding disposed on said one leg, said primary and secondary windings being relatively loosely coupled thereby to provide said windings with high leakage reactance, a condenser having a value of capacity such that when connected across said secondary winding and the transformer is excited with a voltage of predetermined magnitude and frequency a condition of a series resonant nature exists at the said frequency, a third winding on said one leg, a low reluctance shunt disposed between said third winding and said secondary winding, high reluctance means in said one leg beyond said shunt, and means for connecting a load circuit to at least a certain portion of said secondary winding.

9. A transformer having substantially constant output voltage and a substantially harmonic free output voltage comprising, a core, a primary winding disposed on one leg of said core, a secondary winding disposed on said one leg, said primary and secondary windings being relatively loosely coupled thereby to provide said windings with high leakage reactance, said high leakage reactance means including a magnetic shunt having a nonmagnetic gap, a condenser having a value of capacity such that when connected across said secondary winding and the transformer is excited with a voltage of predetermined magnitude and frequency a condition of a series resonant nature exists at the said frequency, a third winding on said one leg, a low reluctance shunt disposed between said third winding and said secondary winding, high reluctance means in said core beyond said shunt, said high reluctance means including a core portion and a nonmagnetic gap, and means for connecting a load circuit to at least a certain portion of said secondary winding.

10. A transformer having substantially constant output voltage and a substantially harmonic free output voltage comprising, a core, a primary winding and a secondary winding on said core, a high reluctance shunt magnetically disposed between said windings, a third winding disposed on said core in a position to link With a portion of the leakage flux of said secondary winding and to be substantially free of any linkage with the leakage flux of said primary winding, a condenser, said secondary winding, said third winding and said condenser being connected in circuit, said condenser having a value of capacity such that when the transformer is excited with a voltage of predetermined magnitude and frequency a condition of a series resonant nature exists at the said frequency, and means for connecting a load circuit to at least a certain portion of said secondary winding.

ll. A transformer having substantially constant output voltage and a substantially harmonic free output voltage comprising, a core, a primary winding and a secondary winding on said core, a high reluctance shunt magnetically disposed between said windings, a third winding disposed on said core in a position to link with a portion of the leakage flux of said secondary winding and to be substantially free of any linkage with the leakage flux of said primary winding, a condenser, said third winding in additive polarity to said secondary winding and said condenser being connected in circuit with said secondary winding, said condenser having a value of capacity such that when the transformer is excited with a voltage of predetermined magnitude and frequency a condition of a series resonant nature exists at the said frequency, and means for connecting a load circuit to at least a certain portion of said secondary winding.

12. A transformer having substantially constant output voltage and a substantially harmonic free output voltage comprising, a core, a primary winding and a secondary winding on said core and having high leakage reactance associated therewith, a condenser having value of capacity such that when connected across said secondary winding and the transformer is excited with a voltage of predetermined magnitude and frequency a condition of a series resonant nature exists at the said frequency, a third winding disposed on said core in a position to link with a portion of the leakage flux of said secondary winding and to be substantially free of any linkage with the leakage flux of said primary winding, said secondary winding, said third winding and said condenser being connected in a series circuit with said third winding in additive polarity relative to said secondary winding, and means for connecting a load circuit to at least a certain portion of said secondary winding.

13. A transformer having substantially constant output voltage and a substantially harmonic free output voltage comprising, a core, a primary winding and a secondary Winding on said core, said primary and secondary windings being relatively loosely coupled thereby to provide said windings with high leakage reactance, a condenser having a value of capacity such that when connected across said secondary winding and the transformer is excited with a voltage of predetermined magnitude and frequency a condition of a series resonant nature exists at the said frequency, a third winding disposed on said core in a position to link with a portion of the leakage flux of said secondary winding and to be substantially free of any linkage with the leakage flux of said primary winding, said secondary winding, said third Winding and said condenser being connected in circuit with said third winding in additive polarity to said secondary winding, and means for connecting a load circuit to at least a certain portion of said secondary winding.

14. A transformer having substantially constant output voltage and a substantially harmonic free output voltage comprising, a core, a primary winding and a secondary winding on said core, said primary and secondary windings being relatively loosely coupled thereby to provide said windings with high leakage reactance, a condenser having a value of capacity such that when connected across said secondary winding and the transformer is excited with a voltage of predetermined magnitude and frequency a condition of a series resonant nature exists at the said frequency, a third winding disposed on said core in a position to link with a portion of the leakage flux of said secondary winding and to be substantially free of any linkage with the leakage flux of said primary winding, said secondary winding, said third winding and said condenser being connected in circuit with said third winding in additive polarity to 11 said secondary Winding, a compensating winding disposed on said core in close coupled relationship with said primary winding and Connected in bucking relationship to said secondary winding, and means for connecting a load circuit to at least a certain portion of said secondary Winding and to said compensating Winding.